WO1999004486A1 - Signal processing system - Google Patents
Signal processing system Download PDFInfo
- Publication number
- WO1999004486A1 WO1999004486A1 PCT/GB1998/002099 GB9802099W WO9904486A1 WO 1999004486 A1 WO1999004486 A1 WO 1999004486A1 GB 9802099 W GB9802099 W GB 9802099W WO 9904486 A1 WO9904486 A1 WO 9904486A1
- Authority
- WO
- WIPO (PCT)
- Prior art keywords
- phase
- signal
- signal processing
- processing system
- feedback
- Prior art date
Links
- 238000012545 processing Methods 0.000 title claims abstract description 32
- 230000010363 phase shift Effects 0.000 claims abstract description 26
- 238000012937 correction Methods 0.000 claims description 2
- 230000000694 effects Effects 0.000 claims description 2
- 238000000034 method Methods 0.000 description 14
- 230000005540 biological transmission Effects 0.000 description 10
- 238000006243 chemical reaction Methods 0.000 description 5
- 230000003595 spectral effect Effects 0.000 description 4
- 230000003321 amplification Effects 0.000 description 3
- 238000003199 nucleic acid amplification method Methods 0.000 description 3
- 230000002238 attenuated effect Effects 0.000 description 2
- 238000010586 diagram Methods 0.000 description 2
- 238000005516 engineering process Methods 0.000 description 2
- 238000004519 manufacturing process Methods 0.000 description 2
- 108010076504 Protein Sorting Signals Proteins 0.000 description 1
- 230000001419 dependent effect Effects 0.000 description 1
- 238000013461 design Methods 0.000 description 1
- 230000008030 elimination Effects 0.000 description 1
- 238000003379 elimination reaction Methods 0.000 description 1
- 230000010354 integration Effects 0.000 description 1
- 238000012544 monitoring process Methods 0.000 description 1
- 238000001228 spectrum Methods 0.000 description 1
- 238000009966 trimming Methods 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
- H03F1/34—Negative-feedback-circuit arrangements with or without positive feedback
- H03F1/345—Negative-feedback-circuit arrangements with or without positive feedback using hybrid or directional couplers
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
- H03F1/32—Modifications of amplifiers to reduce non-linear distortion
- H03F1/3241—Modifications of amplifiers to reduce non-linear distortion using predistortion circuits
- H03F1/3247—Modifications of amplifiers to reduce non-linear distortion using predistortion circuits using feedback acting on predistortion circuits
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F2200/00—Indexing scheme relating to amplifiers
- H03F2200/57—Separate feedback of real and complex signals being present
Definitions
- the present invention relates to a signal processing system which uses Cartesian loop control.
- the present invention relates to a system which may be used for linearising a power amplifier for use in, for example, a radio transmitter which, in turn, may be used in, for example, a VHF digital air traffic control communications system.
- One particular method of feedback control is that of Cartesian feedback control, wherein a control input is split into orthogonal components - an in-phase and a quadrature component - and a feedback signal is similarly split. Feedback is then carried out using these split control input and feedback signals.
- Cartesian feedback control is in the linearisation of amplifier stages.
- a particular application of linearised amplifier stages is in radio transmitters .
- Fig. 1 shows a schematic drawing of a conventional radio transmitter.
- a signal to be transmitted is created at block 1 - via a microphone, for example; this signal is then processed in block 2 - modulated, converted to an appropriate frequency for transmission etc.; the processed signal is then amplified (3) and transmitted via some form of antenna (4).
- the purity of the spectrum has to be very high. This is especially true for applications where a fixed waveband has been allocated for a particular use and there is a desire to get as many users into the available waveband as possible.
- Such applications include, for example: air traffic control, mobile telephones, radio and television station broadcasts .
- Cartesian loop control requires control of phase shift around the loop, and this introduces problems with tuning the transmitter over a band of frequencies .
- the transmitter has to be readjusted each time the transmission frequency is changed.
- Prior art controllers used phase-shifting networks operating at radio frequency (RF). These RF phase-shift networks are difficult to design and limited in their phase control range, frequently making it necessary to introduce phase control at more than one point in the circuit. Furthermore, they are subject to drift with time and temperature. If a transmitter is to cover anything other than an extremely narrow band of frequencies, the RF phase-shifting networks need to be readjusted each time a frequency change is made. This is either done manually, which is time consuming and requires skilled personnel, or automatically controlled, e.g. by a microprocessor, which places further demands on the RF phase-shifting network.
- FIG. 2 A conventional Cartesian feedback apparatus, such as that described in Petrovic's paper (supra), is shown in Fig. 2.
- the error signals (lerr, Qerr) are used directly to control the magnitude of the I and Q components derived from the VCO (Voltage Controlled Oscillator) and thus control the magnitude and phase of the transmitter output.
- VCO Voltage Controlled Oscillator
- An object of the present invention is to provide a signal processing system and method which very accurately control a downstream component or system over a wide band of frequencies, using a feedback technique which has the advantages of Cartesian loop control mentioned above and which does not have the difficult component-matching requirements of some of the techniques mentioned above.
- a signal processing system which comprises: at least one control loop having a forward path and a feedback path; signal processing means for producing a representation of the desired downstream output amplitude and phase as a pair of substantially orthogonal signal components ; feedback-path splitting means for splitting a feedback signal into a plurality of substantially orthogonal feedback signal components; first combining means for combining the substantially orthogonal feedback signal components with the corresponding substantially orthogonal signal components to create error signals; a plurality of modulating means which control the amplitude, frequency and/or phase of the pair of substantially orthogonal signal components on the basis of control signals which are derived from the error signals; and second combining means for combining the outputs of said plurality of modulating means into an output signal; wherein, said signal processing system further comprises a phase-shift control means in the forward path of the control loop which derives said control signals from said error signals on the basis of monitored signal values from at least one predetermined point in the signal processing system.
- Such a system has the advantages that it provides the very high accuracy of Cartesian feedback control for the control of downline components or systems whilst being able to operate over a wide band of operating frequencies and that it does not have the difficult component-matching requirements or transmitter/receiver atching requirements of some other systems .
- This latter advantage means that the system of the invention is easily repeatable - it may be produced in large quantities without the need for extended set-up and trimming procedures which are both time-consuming and costly. Using such a set-up, the phase may be adjusted at will - anywhere between 0° and 360°.
- the second phase-shift control means may operate at baseband frequency - allowing the use of simple, repeatable and cheap components; the phase-shift control means may be digital; the phase-shift control means may be digitally controlled; the phase-shift control means may be auto- calibrated. This could be achieved in situations where an initialising input signal sequence (a "preamble") is known and the phase-shift control means can check what the feedback is for this known sequence, then, if the feedback is wrong, it can be automatically trimmed accordingly; if the phase-shift control means is digitally controlled, it may be made self-calibrating using the same principle as for auto-calibration and running a simple algorithm in the digital control means in order to self-trim the phase-shift control means.
- phase-shift control means can also be used to control the gain of the control loop and thus be used to compensate for variable gains within other loop components .
- Fig. 1 is a schematic drawings of a conventional radio transmitter.
- Fig. 2 is a schematic drawing of a signal processing system using conventional Cartesian feedback control.
- Fig. 3 is a schematic depiction of a prior art up- conversion and combination means as conventionally used in Cartesian feedback control.
- Fig. 4 is a schematic depiction of the signal processing system of this invention in use controlling a power amplifier.
- Fig. 5 is a more detailed system diagram for a radio transmitter circuit which uses the signal processing system of this invention.
- Fig. 6 is a detailed system diagram for a radio transceiver which uses the signal processing system of this invention.
- Fig. 4 is a schematic depiction of the signal processing system of this invention in use controlling a power amplifier.
- a signal which is to be transmitted (x(t)) is split into an in-phase and a quadrature component (I(t) and Q(t)) by a forward-path splitting means.
- In- phase and quadrature feedback components are then subtracted from the input signal components to form error signals (lerr and Qerr). This subtraction is done by comparators 6 and 7.
- the resultant error signals are then passed through phase-shift control means (12) to an I-Q modulation means (8) which modulates and combines the in-phase and quadrature error signals (lerr and Qerr) to form a pre-amplification output signal y(t).
- This pre-amplification output signal then passes to the power amplifier (PA) (3) and subsequently to an antenna means (4) for transmission.
- the amplified output signal passes through a coupler (9) from which this signal is fed back through an attenuator (11).
- the attenuated feedback signal (y'(t)) is split into in-phase and quadrature feedback components (Ifb and Qfb) by an I-Q demodulation means (10) and these feedback components are then combined with the input signal components (I(t) and Q(t)) as described above.
- the phase-shift control means (12) is digitally controlled and has monitor inputs connected to various points of the circuit.
- the monitor inputs are from the transmission signal at terminal 13, from the in-phase and quadrature feedback components at terminals 14 and 15 and from the in-phase and quadrature error signals at terminals 16 and 17, though additional monitor inputs could also be taken or a selection from these inputs may be sufficient in other circumstances.
- the phase-shift control means (12) accurately controls the phase shift of the signals based directly on the monitor inputs .
- Fig. 5 shows a particular embodiment of the invention in a radio transmitter circuit.
- PA Control Module The present invention is embodied in the PA control module 18, which is labelled "PA Control Module”.
- PA Control Module The numerals, as used in preceding paragraphs, represent the same system parts and a repeated description of these parts is omitted.
- the frequency range f A to f 5 is the desired range of radio transmission frequencies which are to be produced by the transmitter.
- An oscillator (19) is connected to the I-Q modulation and demodulation means (8, 10) via a signal splitter (20), in order to up-convert/down-convert the incoming signals to an intermediate frequency (IF), f j - intermediate between baseband and the particular desired transmission frequency.
- the signal in the forward path passes, via a buffer (24) to an up-conversion means (22) which up-converts the signal to a higher, radio frequency (RF), between f 2 and f 3 , which is close to the desired transmission frequency (ie. close to the desired frequency which is in the range of f 4 to f 5 ) .
- RF radio frequency
- This up- conversion from IF to RF is carried out using a synthesizer circuit (24) which is connected to the up- conversion means (22) via a signal splitter (23).
- the synthesizer is controlled to produce a signal at the desired frequency within the wide band of frequencies between f 2 and f 3 .
- the outgoing signal is then passed through a pair of tunable filters (25, 26) which are separated by a buffer circuit (26). These filters are controlled by a processor (28) in order to further increase the spectral accuracy of the radio transmitter. In a similar manner to the phase control, this frequency control is based on monitored signal values from at least one predetermined point (13-17) in the signal processing system.
- the output of the second tunable filter (27) is output to the downline circuit which is to be controlled, in this case a power amplifier (3).
- the output of the downline circuit which is to be controlled is sensed at a coupler (9) and is appropriately attenuated by an attenuator (11).
- This feedback signal is then down-converted to an intermediate frequency (IF) by a down-conversion means (21) which is connected via a signal splitter (23) to the synthesizer module (24).
- This IF feedback signal is then down-converted to baseband and split into two substantially orthogonal feedback signals (Ifb, Qfb) by the I-Q demodulation means (10) which is connected to an oscillator (19) via signal splitting means (20).
- the two substantially orthogonal feedback signals (Ifb, Qfb) are fed back, via two buffer circuits (29, 30) to differencing means (6, 7) where they are combined with the input signal components (I(t), Q(t)) and subsequently integrated by integration circuits (31, 32) to farm the error signals (lerr, Qerr).
- the splitting of the input signal (x(t)) into substantially orthogonal components (I(t), Q(t)) is carried out by a Digital Signal Processing (DSP) Module (5).
- DSP Digital Signal Processing
- the input signal (x(t)) is converted into digital form by an analogue-digital converter (44), then appropriately split by a digital signal processor (39) and subsequently, the two substantially orthogonal signal components are converted back into analogue form by digital-analogue converters (42, 43).
- the control loop of the second phase-shift control means (12) is closed via a multiplexer (41), and analogue-digital converter (40), a digital signal processor (39) and a slave processor (28). This same control loop is used to control the tunable filters (25, 27) at the output stage of the PA control module (18).
- a final bandpass filter (53) is provided after the feedback coupler (9), for effecting elimination of unwanted transmitter harmonics .
- the transmitter formatter module (54) allows the radio transmitter system to be used for sending voice data which may be input from a microphone (not shown) which would be plugged into a microphone socket (48) of the front panel (33, 55) of the radio transmitter or for sending data from other sources, ie. any sort of data, including voice data or computer data .
- Non-voice data or remote voice data may be input via a connector (52).
- Such data is then appropriately formatted by the transmitter formatter Module (54) and passed on to the transmitter DSP module (5) for splitting into substantially orthogonal signal components (I(t), Q(t)).
- circuits 34, 35 are also provided for controlling the bias of the power amplifier (3), based on its operating temperature.
- a variety of monitoring, controlling and failsafe circuits are also provided (36,
- the radio transmitter circuit of Fig. 5 may be used with a separate receiver circuit or it may be combined with a receiver circuit in order to form a transceiver circuit such as that in Fig. 7.
- Loopback mode operation is operation where the receiver side of the transceiver is used to monitor the output of the transmitter side.
- this loopback mode may be realised with a very simplified reception function, since the signal being monitored is strong, with a high signal- to-noise ratio and the direction which the signals are coming from is known.
- part of the two DSP chips (39, 55) is configured to operate as a receiver; part of the two DSP chips (39, 55) is configured to run as a transmitter and part of the chips (39, 55) is configured to run as a very much simplified receiver - using a reduced sample rate.
- This innovative use of the chips allows the transceiver to be built using only two DSP chips with a corresponding cost reduction in manufacture.
- the present invention presents a method of improving Cartesian loop control systems which allows the use of a Cartesian loop in a system operating over a wide band of frequencies as a stable means to implement phase correction.
Abstract
Description
Claims
Priority Applications (5)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
AU83512/98A AU745842B2 (en) | 1997-07-18 | 1998-07-16 | Signal processing system |
US09/462,485 US6687312B1 (en) | 1997-07-18 | 1998-07-16 | Signal processing system |
EP98933819A EP1016210B1 (en) | 1997-07-18 | 1998-07-16 | Signal processing system |
DE69818075T DE69818075T2 (en) | 1997-07-18 | 1998-07-16 | SIGNAL PROCESSING SYSTEM |
AT98933819T ATE249692T1 (en) | 1997-07-18 | 1998-07-16 | SIGNAL PROCESSING SYSTEM |
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
GB9715278.9 | 1997-07-18 | ||
GB9715278A GB9715278D0 (en) | 1997-07-18 | 1997-07-18 | Signal processing system |
Publications (1)
Publication Number | Publication Date |
---|---|
WO1999004486A1 true WO1999004486A1 (en) | 1999-01-28 |
Family
ID=10816151
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
PCT/GB1998/002099 WO1999004486A1 (en) | 1997-07-18 | 1998-07-16 | Signal processing system |
Country Status (7)
Country | Link |
---|---|
US (1) | US6687312B1 (en) |
EP (1) | EP1016210B1 (en) |
AT (1) | ATE249692T1 (en) |
AU (1) | AU745842B2 (en) |
DE (1) | DE69818075T2 (en) |
GB (1) | GB9715278D0 (en) |
WO (1) | WO1999004486A1 (en) |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
WO2001024472A1 (en) * | 1999-09-29 | 2001-04-05 | Rohde & Schwarz Gmbh & Co. Kg | Transmitting-receiving device comprising a closed cartesian feedback loop |
WO2001024467A2 (en) * | 1999-09-29 | 2001-04-05 | Rohde & Schwarz Gmbh & Co. Kg | Method for adjusting a phase angle of a phase modifier of a transmitting device |
Families Citing this family (6)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
KR100382487B1 (en) * | 2000-11-02 | 2003-05-09 | 엘지전자 주식회사 | System for gaining compensation and the phase distortion gain in Mobile transmission communication |
GB2400250B (en) * | 2003-03-31 | 2005-05-25 | Motorola Inc | Wireless communication unit and linearised transmitter circuit therefor |
DE102005010483A1 (en) | 2005-03-04 | 2006-09-14 | Reinhold Schmidt | With a device to be secured cooperating security device |
US8275071B2 (en) * | 2007-05-17 | 2012-09-25 | Harris Stratex Networks Operating Corporation | Compact dual receiver architecture for point to point radio |
US8095088B2 (en) | 2007-05-17 | 2012-01-10 | Harris Stratex Networks Operating Corporation | Compact wide dynamic range transmitter for point to point radio |
US7782765B2 (en) | 2007-01-22 | 2010-08-24 | Harris Stratex Networks Operating Corporation | Distributed protection switching architecture for point-to-point microwave radio systems |
Citations (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4462001A (en) * | 1982-02-22 | 1984-07-24 | Canadian Patents & Development Limited | Baseband linearizer for wideband, high power, nonlinear amplifiers |
US5111155A (en) * | 1991-03-04 | 1992-05-05 | Motorola, Inc. | Distortion compensation means and method |
US5574992A (en) * | 1994-04-29 | 1996-11-12 | Motorola, Inc. | Method and apparatus for reducing off-channel interference produced by a linear transmitter |
Family Cites Families (20)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US5023940A (en) | 1989-09-01 | 1991-06-11 | Motorola, Inc. | Low-power DSP squelch |
US5066923A (en) * | 1990-10-31 | 1991-11-19 | Motorola, Inc. | Linear transmitter training method and apparatus |
US5134718A (en) | 1990-10-31 | 1992-07-28 | Motorola, Inc. | Fast phase shift adjusting method and device for linear transmitter |
GB2265269B (en) | 1992-03-02 | 1995-08-30 | Motorola Ltd | Radio transmitter with linearization training sequence |
SE470455B (en) | 1992-08-24 | 1994-04-11 | Ericsson Telefon Ab L M | Device for compensating the phase rotation in the feedback loop of a Cartesian feedback power amplifier |
GB2272589B (en) * | 1992-11-16 | 1995-11-29 | Linear Modulation Tech | Automatic calibration of the quadrature balance within a cartesian amplifier |
US5386198A (en) | 1993-01-28 | 1995-01-31 | Telefonaktiebolaget L M Ericsson | Linear amplifier control |
US5551070A (en) | 1993-01-28 | 1996-08-27 | Telefonaktiebolaget Lm Ericsson | Cartesian multicarrier feedback |
US5420536A (en) | 1993-03-16 | 1995-05-30 | Victoria University Of Technology | Linearized power amplifier |
US5351016A (en) | 1993-05-28 | 1994-09-27 | Ericsson Ge Mobile Communications Inc. | Adaptively self-correcting modulation system and method |
GB9316869D0 (en) | 1993-08-13 | 1993-09-29 | Philips Electronics Uk Ltd | Transmitter and power amplifier therefor |
WO1995006354A1 (en) | 1993-08-20 | 1995-03-02 | Motorola, Inc. | Radio transmitter with power amplifier linearizer |
US5535247A (en) * | 1993-09-24 | 1996-07-09 | Motorola, Inc. | Frequency modifier for a transmitter |
GB9320078D0 (en) | 1993-09-29 | 1993-11-17 | Linear Modulation Tech | Cartesian amplifier power control and related applications |
GB2283629B (en) | 1993-10-26 | 1997-08-27 | Motorola Ltd | Radio communications apparatus |
GB2286302B (en) | 1994-01-29 | 1998-12-16 | Motorola Inc | Power amplifier and radio transmitter |
GB2293935B (en) | 1994-10-03 | 1999-07-14 | Linear Modulation Tech | Automatic calibration of carrier suppression and loop phase in a cartesian amplifier |
GB2301247A (en) | 1995-05-22 | 1996-11-27 | Univ Bristol | A cartesian loop transmitter amplifier |
US5652534A (en) * | 1995-12-21 | 1997-07-29 | Hughes Aircraft Company | Precision digital phase shifter |
US5742201A (en) * | 1996-01-30 | 1998-04-21 | Spectrian | Polar envelope correction mechanism for enhancing linearity of RF/microwave power amplifier |
-
1997
- 1997-07-18 GB GB9715278A patent/GB9715278D0/en not_active Ceased
-
1998
- 1998-07-16 US US09/462,485 patent/US6687312B1/en not_active Expired - Lifetime
- 1998-07-16 AU AU83512/98A patent/AU745842B2/en not_active Expired
- 1998-07-16 AT AT98933819T patent/ATE249692T1/en not_active IP Right Cessation
- 1998-07-16 WO PCT/GB1998/002099 patent/WO1999004486A1/en active IP Right Grant
- 1998-07-16 EP EP98933819A patent/EP1016210B1/en not_active Expired - Lifetime
- 1998-07-16 DE DE69818075T patent/DE69818075T2/en not_active Expired - Lifetime
Patent Citations (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4462001A (en) * | 1982-02-22 | 1984-07-24 | Canadian Patents & Development Limited | Baseband linearizer for wideband, high power, nonlinear amplifiers |
US5111155A (en) * | 1991-03-04 | 1992-05-05 | Motorola, Inc. | Distortion compensation means and method |
US5574992A (en) * | 1994-04-29 | 1996-11-12 | Motorola, Inc. | Method and apparatus for reducing off-channel interference produced by a linear transmitter |
Non-Patent Citations (1)
Title |
---|
MANSELL A R ET AL: "TRANSMITTER LINEARISATION USING COMPOSITE MODULATION FEEDBACK", ELECTRONICS LETTERS, vol. 32, no. 23, 7 November 1996 (1996-11-07), pages 2120/2121, XP000643852 * |
Cited By (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
WO2001024472A1 (en) * | 1999-09-29 | 2001-04-05 | Rohde & Schwarz Gmbh & Co. Kg | Transmitting-receiving device comprising a closed cartesian feedback loop |
WO2001024467A2 (en) * | 1999-09-29 | 2001-04-05 | Rohde & Schwarz Gmbh & Co. Kg | Method for adjusting a phase angle of a phase modifier of a transmitting device |
WO2001024467A3 (en) * | 1999-09-29 | 2001-09-27 | Rohde & Schwarz | Method for adjusting a phase angle of a phase modifier of a transmitting device |
US6977968B1 (en) | 1999-09-29 | 2005-12-20 | Rohde & Schwarz Gmbh & Co. Kg | Transmitting-receiving device comprising a closed cartesian feedback loop |
US7020216B1 (en) | 1999-09-29 | 2006-03-28 | Rohde & Schwarz Gmbh & Co Kg | Method for adjusting a phase angle of a phase modifier of a transmitting device |
Also Published As
Publication number | Publication date |
---|---|
GB9715278D0 (en) | 1997-09-24 |
AU745842B2 (en) | 2002-04-11 |
US6687312B1 (en) | 2004-02-03 |
ATE249692T1 (en) | 2003-09-15 |
AU8351298A (en) | 1999-02-10 |
DE69818075T2 (en) | 2004-06-17 |
EP1016210A1 (en) | 2000-07-05 |
DE69818075D1 (en) | 2003-10-16 |
EP1016210B1 (en) | 2003-09-10 |
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