WO1984004216A1 - Simultaneous transmission of speech and data over an analog channel - Google Patents

Simultaneous transmission of speech and data over an analog channel Download PDF

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Publication number
WO1984004216A1
WO1984004216A1 PCT/US1984/000483 US8400483W WO8404216A1 WO 1984004216 A1 WO1984004216 A1 WO 1984004216A1 US 8400483 W US8400483 W US 8400483W WO 8404216 A1 WO8404216 A1 WO 8404216A1
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Prior art keywords
signal
receiver
data
speech
data signal
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PCT/US1984/000483
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French (fr)
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Edward Ashford Lee
David Goodwin Shaw
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American Telephone & Telegraph
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Publication of WO1984004216A1 publication Critical patent/WO1984004216A1/en

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    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04JMULTIPLEX COMMUNICATION
    • H04J1/00Frequency-division multiplex systems
    • H04J1/20Frequency-division multiplex systems in which at least one carrier is angle-modulated
    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04MTELEPHONIC COMMUNICATION
    • H04M11/00Telephonic communication systems specially adapted for combination with other electrical systems
    • H04M11/06Simultaneous speech and data transmission, e.g. telegraphic transmission over the same conductors
    • H04M11/062Simultaneous speech and data transmission, e.g. telegraphic transmission over the same conductors using different frequency bands for speech and other data

Definitions

  • the present invention relates to a technique for recovering analog speech and modulated data simultaneously t ransmi tted over an analog channel with the capability at the receiver of separating the two simultaneously received signals and substantially improving the cancellation of the data from the speech by compensating for phase jitter and frequency offset in the recovered data signal.
  • a method of transmitting data and speech signals in a telephone system in which communication is effected via a radio link is disclosed in U. S. Patent 4,280,020 issued to L. E. Schnurr on July 21, 1981.
  • the data and speech signals are separated in the frequency domain and transmitted in respective separate sideband channels, the data sideband channel containing sidebands generated by time coding an otherwise continuous wave signal.
  • a spread spectrum arrangement for (de)multiplexing speech signals and nonspeech signals is disclosed in U. S. Patent 4,313,197 issued to N. F. Maxemchuk on January 26, 1982.
  • a block of speech signals may be converted from the time domain to a frequency domain by a Fourier transformation.
  • a Fourier component may be pseudo-randomly selected from a subset of such components. Responsive to the selected components, a prediction of the component may be substituted therefor, the prediction being thereafter modified, e.g., by its amplitude being incremented or decremented to reflect the multiplexing of a logic 1 or a logic 0 nonspeech signal. The modified prediction may be converted back to the time domain for transmission to the receiver. At the receiver, a parallel demultiplexing occurs for extracting speech signals and nonspeech signals for the multiplexed signals.
  • the samples are sent without modification; however, if a logical 1 is present, frequency inversion scrambling of the samples occurs.
  • the receiver performs the inverse process to recover both the speech and data.
  • the foregoing problem has been solved in accordance with the present invention which relates to a technique for the simultaneous transmission of analog speech and modulated data over an analog channel with the capability at the receiver of separating the two simultaneously received signals and substantially improving the cancellation of the data signal from the speech signal by compensating for phase jitter and frequency offset in the recovered data signal.
  • the data is detected and is remodulated and then subtracted, via an adaptive filter, from the transmitted and received signal to yield the recovered speech.
  • the weights used in the adaptive filter are adjusted by a device implementing the least mean square algorithm to enable maximum removal of the data signal from the received composite speech and data signal.
  • FIG. 1 is a block diagram of a preferred transmitter and receiver arrangement for transmitting simultaneous speech and Multilevel Phase Shift Keyed (MPSK) modulated data signals
  • FIG. 2 is a plot of the power density (db) vs frequency averaged for exemplary speech spoken by male and female speakers and a predetermined baud rate data signal transmitted in accordance with the present invention
  • FIG. 3 illustrates exemplary curves of the Bit Error Rate (BER) vs data-to-speech power ratio (DSPR) for a data bit rate of 500 bits/sec. for BPSK data carrier frequencies ranging from 500 to 2500 Hz and for Gaussian noise; and
  • BER Bit Error Rate
  • DSPR data-to-speech power ratio
  • FIG. 4 are plots of exemplary BER vs DSPR curves for bit rates between 250 and 1000 bits/sec, where the BPSK data carrier frequency is 2500 Hz.
  • FIG. 1 A block diagram of a preferred arrangement of a system in accordance with the present invention which transmits analog speech and data signals simultaneously is shown in FIG. 1.
  • the system comprises a transmitter 10 which receives a speech signal and a data signal as inputs from external sources not shown.
  • the speech signal can be bandpass filtered in optional filter 12 to an exemplary frequency band of, for example, 200 Hz to 3200 Hz if desired.
  • the resultant speech signal S (t) is then scaled by a factor ⁇ in multiplier 14 and transmitted to an adder 16.
  • the input data signal is modulated in a modulator 18 with a predetermined carrier frequency f c , which hereinafter will take the exemplary form of a Multilevel Phase Shift Keyed (MPSK) carrier within the analog speech signal frequency band of, for example, 2500 Hz to generate a MPSK modulated data signal D (t) which can include raised cosine pulse shaping.
  • MPSK Multilevel Phase Shift Keyed
  • the resultant exemplary MPSK modulated data signal is added to the weighted speech signal in adder 16 to produce the transmitted signal X (t) over the analog transmission channel 20.
  • X (t) passes through an analog transmission channel 20.
  • this channel can be described by its impulse response, H ch(t) .
  • ⁇ he receiver 30 sees the transmitted signal as the convolution of the channel impulse response and the transmitted signal, i.e.,
  • Receiver 30 recovers the data portion of the received signal in a conventional manner using any suitable carrier recovery arrangement 32 and MPSK demodulator 33.
  • Demodulator 33 comprises a decoder and decision section which has the capability of (a) decoding the received data signal for transmission to both a first output of the receiver and a remodulator 34 and (b) generating phase error information relating to phase jitter and frequency offset in the data signal of the received composite signal .
  • This phase error information signal includes raw information relating to, for example, long distance microwave or satellite transmission carrier mismatch and local power frequencies and certain harmonics thereof. In the United States, these frequencies would be, for example, 60, 120 and 180 Hz. In Europe, for example, such frequencies might be 50, 100 and 150 Hz.
  • the raw phase error signal is processed to generate an appropriate phase error signal in a Phase Error Tracking Circuit 38.
  • Phase Error Tracking Circuit 38 can comprise any suitable circuit known in the art as, for example, separate bandpass filters for each of the frequencies of interest; a low pass filter to, for example, pass up to 500 Hz; or an Adaptive Phase-Jitter Tracker disclosed, for example, in U. S. Patent 4,320,526 issued to R. D. Gitlin on March 16, 1982.
  • the performance of the data signal recovery portion of receiver 30 depends largely upon the system parameter ⁇ . From equation (1) it can be seen that the data signal D (t) must be detected in the presence of the speech signal S (t) .
  • the system parameter ⁇ is adjusted to make the speech power, , small enough for reliable data recovery.
  • the speech signal is recovered by subtracting the data signal component from the appropriately synchronized composite signal . This is accomplished by first regenerating the data signal in MPSK remodulator 34, which corresponds in function to MPSK modulator 18 at the transmitter 10. Timing for the MPSK remodulator 34 is obtained from the carrier recovery circuit 32. In addition, the phase error information from Phase Error Tracking Circuit 38 is introduced into the regenerated data signal in a manner to substantially improve cancellation of the data signal in the resultant recovered speech signal at a second output of the receiver when the regenerated data signal is subtracted from the received composite signal .
  • the remodulator can comprise any suitable circuit such as, for example, a first phase encoding section which includes a phase modulator for converting the data into a phase differential encoded signal which is modified by the retrieved phase error information, and a second modulator section which modulates the resultant signal from the first section into the regenerated data signal .
  • the data signal is not subtracted directly from the received composite signal to recover the speech signal until the effects of channel 20 have been accounted for. To do this, an estimate of the channel response H ch(t) . must be made after which the speech signal is recovered via
  • Carrier Recovery circuit 32 and MPSK demodulator 33 with Gaussian interference is well understood.
  • the interference is speech
  • the receiver performance requires special attention.
  • Gaussian noise has a uniform frequency distribution, so when the data bit- error-rate (BER) is looked at, the MPSK carrier frequency is not important.
  • the power density of speech is not uniform with frequency, but rather decreases rapidly as the frequency increases as shown in FIG. 2 for curve 40.
  • the MPSK carrier frequency is expected to play an important role in the BER performance since it is only that portion of the interference falling within the same bandwidth as the data signal which contributes to its detriment.
  • a typical data signal with a Binary Phase Shift Keyed (BPSK) carrier frequency of 2500 Hz and baud rate of, for example, 250 is also shown in FIG. 2 as curve 41 superimposed on speech signal curve 40.
  • BPSK Binary Phase Shift Keyed
  • FIG. 4 shows the BER performance for different DSPRs when different data rates are used.
  • the BPSK carrier frequency used is the exemplary 2.5 kHz and, as shown, the higher data rates require a higher DSPR for a given BER.
  • the parameter a is adjusted to make the speech power small enough for reliable data recovery. The value of ⁇ can be easily determined from the DSPR as
  • Adaptive FIR filter 35 configured for adaptive cancellation, is found to be very efficient in solving such problems where the regenerated data signal from remodulator 34 is convolved with an arbitrary impulse response .
  • the resultant signal is then subtracted in subtractor 37 from the composite signal X which is synchronized to by any suitable means, such as a delay in the + input leg to subtractor 37 in FIG. 1, leaving the recovered speech .
  • a least mean square (LMS) algorithm is used via circuit 36 to update the impulse response , i.e., used by adaptive filter 35.
  • the parameter ⁇ controls how fast filter 35 converges. Larger value allows fast adaptation, but if ⁇ is too large, instability occurs. In addition small values of ⁇ yield smaller errors between the final and H ch(t) .
  • the theory of the adaptive filter is described in the heretofore mentioned article by Widrow et al in the December 1975 issue of the Proceedings of the IEEE. As a typical example, a FIR filter length of 64 and a ⁇ of 10 -9 was used to achieve a data cancellation in the neighborhood of 33 db.
  • the heretofore described application of the adaptive filter 35 is a special case where the bandwidth of the input data signal does not occupy the entire analog transmission channel bandwidth. In this case, there are many responses which will work with adaptive filter 35.
  • the response outside the bandwidth of the data signal is not defined, so a family of solutions exist. After the LMS algorithm from circuit 36 has converged, will continue to change until it arrives at one of the solutions which creates arithmetic errors in the particular hardware implementation.
  • a simple solution to this problem is to remove the modulation filter found in the MPSK modulator 34 located at receiver 30. The resulting signal would then be broadband.
  • the adaptive filter solution would then be unique and consist of the channel response H ch(t) convolved with the RC filter response.
  • the recovered speech is impaired by channel dispersion, additive channel noise, and imperfect cancellation of the data signal.
  • the speech signal-to-noise ratio (SNR) is used.
  • SNR can be evaluated as
  • N ch is the additive channel noise power while N D is the noise power created by the canceled data signal and is the power of the speech signal.
  • is an important system parameter in deciding the best compromise between recovered data and speech performance.

Abstract

A technique for recovering each of an entire analog speech signal and a modulated data signal simultaneously received over a transmission channel (20) such as a common analog telephone speech channel. In the received composite signal, the entire modulated data signal is multiplexed within the normal analog speech signal frequency band where the speech is present and its signal power density characteristic is at a low level. Separation of the speech and data signals at the receiver (30) is effected by recovering the modulation carrier frequency and demodulating the received signal to recover the data signal. The data signal is then (a) remodulated (34) with the recovered carrier (fc), (b) modified to cancel phase jitter and frequency offset errors detected during the data demodulating process and (c) convolved with an arbitrary channel impulse response in an adaptive filter (35) whose output signal is subtracted from the received composite data and speech signal to generate the recovered speech signal. To improve the recovered speech signal, a least mean square algorithm (36) is used to update the arbitrary channel impulse response output signal of the adaptive filter.

Description

SIMULTANEOUS TRANSMISSION OF SPEECH AND DATA OVER
AN ANALOG CHANNEL
The present invention relates to a technique for recovering analog speech and modulated data simultaneously t ransmi tted over an analog channel with the capability at the receiver of separating the two simultaneously received signals and substantially improving the cancellation of the data from the speech by compensating for phase jitter and frequency offset in the recovered data signal.
Existing analog transmission facilities would be more efficient if speech and data could be simultaneously transmitted over the same channel. Preferably, such a proposal should not compromise the recovered speech and data qualities, neither should there be an expansion in the bandwidth requirements. At the same time, it is desirable to have a system which is simple and cost-effective.
A method of transmitting data and speech signals in a telephone system in which communication is effected via a radio link is disclosed in U. S. Patent 4,280,020 issued to L. E. Schnurr on July 21, 1981. There the data and speech signals are separated in the frequency domain and transmitted in respective separate sideband channels, the data sideband channel containing sidebands generated by time coding an otherwise continuous wave signal. A spread spectrum arrangement for (de)multiplexing speech signals and nonspeech signals is disclosed in U. S. Patent 4,313,197 issued to N. F. Maxemchuk on January 26, 1982. There, at the transmitter, a block of speech signals may be converted from the time domain to a frequency domain by a Fourier transformation. A Fourier component may be pseudo-randomly selected from a subset of such components. Responsive to the selected components, a prediction of the component may be substituted therefor, the prediction being thereafter modified, e.g., by its amplitude being incremented or decremented to reflect the multiplexing of a logic 1 or a logic 0 nonspeech signal. The modified prediction may be converted back to the time domain for transmission to the receiver. At the receiver, a parallel demultiplexing occurs for extracting speech signals and nonspeech signals for the multiplexed signals.
Recently several systems have been proposed to send speech and data simultaneously which exploit the properties of the Short Time Fast Fourier Transform (FFT) and the statistical properties of speech. For example, in the article "Simultaneous Transmission of Speech and Data using Code-Breaking Techniques" by R. Steele et al in BSTJ, Vol. 60, No. 9, November 1981 at pages 2081-2105, a system whereby speech is used as a data carrier is proposed. More particularly, the speech, sampled at 8 kHz, is divided into blocks of N samples, and provided the correlation coefficient and mean square value of the samples exceed system thresholds, data is allowed to be transmitted. If the data is a logical 0, the samples are sent without modification; however, if a logical 1 is present, frequency inversion scrambling of the samples occurs. The receiver performs the inverse process to recover both the speech and data. These techniques can be quite complex and require careful timing and non-dispersive channels. The problem remaining is to provide a technique for the simultaneous transmission of speech and data over an analog channel while compensating at the receiver for various effects produced by the analog channel which technique is simple and cost effective and does not require an expansion in bandwidth requirements.
The foregoing problem has been solved in accordance with the present invention which relates to a technique for the simultaneous transmission of analog speech and modulated data over an analog channel with the capability at the receiver of separating the two simultaneously received signals and substantially improving the cancellation of the data signal from the speech signal by compensating for phase jitter and frequency offset in the recovered data signal.
It is an aspect of the present invention to provide a receiver for recovering from an analog transmission channel, which includes a predetermined channel bandwidth, each of a simultaneously received analog speech signal and a modulated data signal, where the analog speech signal includes a predetermined power density characteristic over the bandwidth of the analog transmission channel and the data signal is received in the portion of the analog transmission channel frequency band where the power density characteristic of the analog speech signal is at a minimal level. At the receiver the data is detected and is remodulated and then subtracted, via an adaptive filter, from the transmitted and received signal to yield the recovered speech. The weights used in the adaptive filter are adjusted by a device implementing the least mean square algorithm to enable maximum removal of the data signal from the received composite speech and data signal. In the process of data detection, information relating to phase jitter and frequency offset is generated and used in remodulating the data in order to substantially improve cancellation of the data signal from the recovered speech signal. Other and further aspects of the present invention will become apparent during the course of the following description and by reference to the accompanying drawings.
Referring now to the drawings, in which like numerals represent like parts in the several views: FIG. 1 is a block diagram of a preferred transmitter and receiver arrangement for transmitting simultaneous speech and Multilevel Phase Shift Keyed (MPSK) modulated data signals; FIG. 2 is a plot of the power density (db) vs frequency averaged for exemplary speech spoken by male and female speakers and a predetermined baud rate data signal transmitted in accordance with the present invention;
FIG. 3 illustrates exemplary curves of the Bit Error Rate (BER) vs data-to-speech power ratio (DSPR) for a data bit rate of 500 bits/sec. for BPSK data carrier frequencies ranging from 500 to 2500 Hz and for Gaussian noise; and
FIG. 4 are plots of exemplary BER vs DSPR curves for bit rates between 250 and 1000 bits/sec, where the BPSK data carrier frequency is 2500 Hz. A block diagram of a preferred arrangement of a system in accordance with the present invention which transmits analog speech and data signals simultaneously is shown in FIG. 1. The system comprises a transmitter 10 which receives a speech signal and a data signal as inputs from external sources not shown. The speech signal can be bandpass filtered in optional filter 12 to an exemplary frequency band of, for example, 200 Hz to 3200 Hz if desired. The resultant speech signal S(t) is then scaled by a factor α in multiplier 14 and transmitted to an adder 16. The input data signal is modulated in a modulator 18 with a predetermined carrier frequency fc, which hereinafter will take the exemplary form of a Multilevel Phase Shift Keyed (MPSK) carrier within the analog speech signal frequency band of, for example, 2500 Hz to generate a MPSK modulated data signal D(t) which can include raised cosine pulse shaping. The resultant exemplary MPSK modulated data signal is added to the weighted speech signal in adder 16 to produce the transmitted signal X(t) over the analog transmission channel 20. The transmitted signal can be defined as x(t)=D(t)+αS(t).
In the present system, the transmitted signal
X(t) passes through an analog transmission channel 20. To a first approximation, this channel can be described by its impulse response, Hch(t). τhe receiver 30 sees the transmitted signal as the convolution of the channel
Figure imgf000006_0001
impulse response and the transmitted signal, i.e.,
Figure imgf000007_0001
Receiver 30 recovers the data portion of the received signal in a conventional manner using any
Figure imgf000007_0002
suitable carrier recovery arrangement 32 and MPSK demodulator 33. Demodulator 33 comprises a decoder and decision section which has the capability of (a) decoding the received data signal for transmission to both a first output of the receiver and a remodulator 34 and (b) generating phase error information relating to phase jitter and frequency offset in the data signal of the received composite signal . This phase error information signal
Figure imgf000007_0003
includes raw information relating to, for example, long distance microwave or satellite transmission carrier mismatch and local power frequencies and certain harmonics thereof. In the United States, these frequencies would be, for example, 60, 120 and 180 Hz. In Europe, for example, such frequencies might be 50, 100 and 150 Hz. The raw phase error signal is processed to generate an appropriate phase error signal in a Phase Error Tracking Circuit 38.
It is to be understood that Phase Error Tracking Circuit 38 can comprise any suitable circuit known in the art as, for example, separate bandpass filters for each of the frequencies of interest; a low pass filter to, for example, pass up to 500 Hz; or an Adaptive Phase-Jitter Tracker disclosed, for example, in U. S. Patent 4,320,526 issued to R. D. Gitlin on March 16, 1982. The performance of the data signal recovery portion of receiver 30 depends largely upon the system parameter α. From equation (1) it can be seen that the data signal D(t) must be detected in the presence of the speech signal S(t). The system parameter α is adjusted to make the speech power,
Figure imgf000007_0004
, small enough for reliable data recovery.
The speech signal is recovered by subtracting the data signal
Figure imgf000008_0002
component from the appropriately synchronized composite signal . This is accomplished
Figure imgf000008_0003
by first regenerating the data signal in MPSK
Figure imgf000008_0004
remodulator 34, which corresponds in function to MPSK modulator 18 at the transmitter 10. Timing for the MPSK remodulator 34 is obtained from the carrier recovery circuit 32. In addition, the phase error information from Phase Error Tracking Circuit 38 is introduced into the regenerated data signal
Figure imgf000008_0005
in a manner to substantially improve cancellation of the data signal in the resultant recovered speech signal at a second output of the receiver when the regenerated data signal is subtracted from the received composite signal
Figure imgf000008_0006
. The remodulator can comprise any suitable circuit such as, for example, a first phase encoding section which includes a phase modulator for converting the data into a phase differential encoded signal which is modified by the retrieved phase error information, and a second modulator section which modulates the resultant signal from the first section into the regenerated data signal
Figure imgf000008_0007
. The data signal
Figure imgf000008_0008
is not subtracted directly from the received composite signal
Figure imgf000008_0009
to recover the speech signal until the effects of
Figure imgf000008_0010
channel 20 have been accounted for. To do this, an estimate of the channel response Hch(t). must be made after which the speech signal
Figure imgf000008_0011
is recovered via
Figure imgf000008_0001
The problem of estimating the channel response
Figure imgf000008_0012
knowing the data signal D(t) and not knowing the random variable speech signal S(t) is solved in accordance with the present invention by the use of an adaptive filter 35. Presently, an adaptive Finite Impulse Response (FIR) filter whose weights are adjusted by the least mean square (LMS) algorithm via device 36 is used for adaptive filter 35. A typical arrangement is shown in FIG. 29 of the article "Adaptive Noise Cancelling: Principles and Applications" by B. Widrow et al in Proceedings of the IEEE, Vol. 63, No. 12, December 1975 at page 1709. The performance of a MPSK receiver, comprising
Carrier Recovery circuit 32 and MPSK demodulator 33, with Gaussian interference is well understood. However, when the interference is speech, the receiver performance requires special attention. White. Gaussian noise has a uniform frequency distribution, so when the data bit- error-rate (BER) is looked at, the MPSK carrier frequency is not important. The power density of speech is not uniform with frequency, but rather decreases rapidly as the frequency increases as shown in FIG. 2 for curve 40. In this case the MPSK carrier frequency is expected to play an important role in the BER performance since it is only that portion of the interference falling within the same bandwidth as the data signal which contributes to its detriment. A typical data signal with a Binary Phase Shift Keyed (BPSK) carrier frequency of 2500 Hz and baud rate of, for example, 250 is also shown in FIG. 2 as curve 41 superimposed on speech signal curve 40.
It has been found that for a given data-to-speech power ratio (DSPR) , better BER performance is obtained when a higher carrier frequency is selected as shown in FIG. 3 using a matched filter receiver. FIG. 4 shows the BER performance for different DSPRs when different data rates are used. In FIG. 4, the BPSK carrier frequency used is the exemplary 2.5 kHz and, as shown, the higher data rates require a higher DSPR for a given BER. As mentioned hereinbefore, the parameter a is adjusted to make the speech power small enough for reliable data recovery. The value of α can be easily determined from the DSPR as
Figure imgf000009_0001
The degree to which the speech signal can be recovered from the composite data and speech signal received in receiver 30 is limited primarily by how well the channel 20 response Hch(t) can be estimated using equation (2). Adaptive FIR filter 35, configured for adaptive cancellation, is found to be very efficient in solving such problems where the regenerated data signal from remodulator 34 is convolved with an arbitrary
Figure imgf000010_0001
impulse response
Figure imgf000010_0002
. The resultant signal is then subtracted in subtractor 37 from the composite signal
Figure imgf000010_0003
X which is synchronized to by any suitable means, such
Figure imgf000010_0004
as a delay in the + input leg to subtractor 37 in FIG. 1, leaving the recovered speech
Figure imgf000010_0005
. To improve the estimate of the recovered speech, a least mean square (LMS) algorithm is used via circuit 36 to update the impulse response , i.e.,
Figure imgf000010_0006
Figure imgf000010_0007
used by adaptive filter 35. After many iterations,
Figure imgf000010_0008
converges from its arbitrary response
Figure imgf000010_0009
to Hch(t), and the recovered speech at the output of subtractor 37 contains little or no noise attributed to the data signal
Figure imgf000010_0010
The re-introduction of phase error information into the remodulated data signal
Figure imgf000010_0011
assists the adaptive filter 35 which is not capable of compensating for the phase error.
The parameter μ controls how fast filter 35 converges. Larger value allows fast adaptation, but if μ is too large, instability occurs. In addition small values of μ yield smaller errors between the final
Figure imgf000010_0012
and Hch(t) . The theory of the adaptive filter is described in the heretofore mentioned article by Widrow et al in the December 1975 issue of the Proceedings of the IEEE. As a typical example, a FIR filter length of 64 and a μ of 10-9 was used to achieve a data cancellation in the neighborhood of 33 db. The heretofore described application of the adaptive filter 35 is a special case where the bandwidth of the input data signal
Figure imgf000011_0002
does not occupy the entire analog transmission channel bandwidth. In this case, there are many responses which will work with adaptive
Figure imgf000011_0003
filter 35. The response outside the bandwidth of the data signal
Figure imgf000011_0004
is not defined, so a family of solutions exist. After the LMS algorithm from circuit 36 has converged,
Figure imgf000011_0005
will continue to change until it arrives at one of the solutions which creates arithmetic errors in the particular hardware implementation. A simple solution to this problem is to remove the modulation filter found in the MPSK modulator 34 located at receiver 30. The resulting signal would then be broadband. The adaptive filter solution
Figure imgf000011_0006
would then be unique and consist of the channel response Hch(t) convolved with the RC filter response.
It is to be understood that the recovered speech is impaired by channel dispersion, additive channel noise, and imperfect cancellation of the data signal. To quantify the recovered speech quality, the speech signal-to-noise ratio (SNR) is used. The SNR can be evaluated as
Figure imgf000011_0001
Nch is the additive channel noise power while ND is the noise power created by the canceled data signal
Figure imgf000011_0007
and is the power of the speech signal. Hereinbefore, it was stated that a smaller value of α yields a better BER. However, from Equation (5) it can be seen that the recovered speech SNR decreases with α and that, if α must be very small, poor recovered speech quality is expected. Therefore, α is an important system parameter in deciding the best compromise between recovered data and speech performance. It is to be understood that the above-described embodiments are simply illustrative of the principles of the invention. Various other modifications and changes may be made by those skilled in the art which will embody the principles of the invention and fall within the spirit and scope thereof. It is to be understood that analog transmission channel 20 can comprise many forms such as, for example, a common telephone channel which operates within the 0-4000 Hz range with unknown amplitude and frequency distortions.

Claims

Claims
1. A receiver characterized by: an input terminal capable of simultaneously receiving an analog speech signal which includes a predetermined power density characteristic over a predetermined bandwidth, and a modulated data signal which is received in a portion of the received analog speech signal bandwidth where the analog speech signal is present and the power density characteristic of the analog speech signal is at a low value; a first and a second output terminal means (33) capable of demodulating the data signal from a received composite analog speech and modulated data signal for transmission to the first output terminal and for generating phase error signals detected in the received data signal; means (34) capable of remodulating the recovered data signal at the output of the demodulating and recovering means while introducing said phase jitter and frequency offset information signals for generating an output signal corresponding substantially to the data signal received at the input terminal of the receiver including said phase error signal; adaptive filtering means (35) capable of generating a first signal representative of an estimate of an impulse response of a channel connected to the input terminal of the receiver, and convolving said first signal with the remodulated data output signal from the remodulating means to generate a resultant output signal; and means (37) capable of subtracting the resultant output signal generated by the adaptive filtering means (35) from the composite analog speech and modulated data signal received at the input terminal of the receiver for substantially canceling the data signal forming part of the composite received signal and generating a resultant output signal at the second output terminal of the receiver which comprises the recovered analog speech signal.
2. A receiver in accordance with claim 1
CHARACTERIZED BY a phase error tracking means (38) responsive to the phase error signals from the demodulating means capable of tracking the phase error at either one of selected frequencies or a selected frequency band associated with interference signals that introduce phase error into the composite signal propagating in the channel connected to the input terminal of the receiver.
3. A receiver in accordance with claim 2,
CHARACTERIZED IN THAT the remodulating means (34) comprises phase encoding means capable of converting the demodulated data signals at the output of the demodulating means (33) to a phase differential encoded signal and reintroducing said phase error signal into the encoded signal; and modulating means responsive to a phase differential encoded signal at the output of the phase encoding means to generate said output signal of the remodulating means.
4. A receiver in accordance with claim 1,
CHARACTERIZED IN THAT the adaptive filtering means (35) comprises means capable of generating said first signal and convolving said first signal with the remodulated data output signal from the remodulating means (34); and means responsive to the resultant output signal from the subtracting means (37) and the remodulated data output signal from the remodulating means for causing a modification of the first signal generated by the generating and convolving means for producing a resultant output data signal of the adaptive filtering means which best cancels the data signal at the second output terminal of the receiver.
5. A receiver in accordance with claim 4, CHARACTERIZED IN THAT the modification means of the adaptive filtering means (35) comprises an arrangement (36) for implementing a least mean square algorithm on sequential synchronized samples of the output signals of both the remodulating and the subtracting means for producing control signals to the generating and convolving means which converge the estimate of an impulse response of the channel connected to the input terminal of the receiver to an actual channel impulse response.
6. A receiver in accordance with claim 1, CHARACTERIZED IN THAT in the adaptive filtering means (35) is adapted to generate a first signal which is an estimate of an impulse response of an analog transmission channel.
7. A receiver in accordance with claim 1, CHARACTERIZED IN THAT the received modulated data signal at the input terminal is a multilevel phase-shift-keyed data signal.
PCT/US1984/000483 1983-04-11 1984-04-02 Simultaneous transmission of speech and data over an analog channel WO1984004216A1 (en)

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IT (1) IT1176002B (en)
WO (1) WO1984004216A1 (en)

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0138988A1 (en) * 1983-04-11 1985-05-02 American Telephone & Telegraph Simultaneous transmission of speech and data over an analog channel.
EP0689337A1 (en) * 1994-06-20 1995-12-27 AT&T Corp. A method for dial-in access security using a multimedia modem
US9118527B2 (en) 2012-10-09 2015-08-25 Fairchild Semiconductor Corporation Data during analog audio

Citations (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3718767A (en) * 1971-05-20 1973-02-27 Itt Multiplex out-of-band signaling system
US3824347A (en) * 1973-02-01 1974-07-16 Ii Communications Corp Voice and data multiplexing system with improved signalling
US3875339A (en) * 1972-09-05 1975-04-01 I I Communications Inc Variable bandwidth voice and data telephone communication system
US4238849A (en) * 1977-12-22 1980-12-09 International Standard Electric Corporation Method of and system for transmitting two different messages on a carrier wave over a single transmission channel of predetermined bandwidth
US4280020A (en) * 1979-01-09 1981-07-21 Essex County Council Radio telephone system with direct digital carrier modulation for data transmission
US4313197A (en) * 1980-04-09 1982-01-26 Bell Telephone Laboratories, Incorporated Spread spectrum arrangement for (de)multiplexing speech signals and nonspeech signals
US4346380A (en) * 1978-12-11 1982-08-24 National Semiconductor Corporation Simultaneous communication of analog and binary information in a single frame of a pulse count modulated digital signal
US4355401A (en) * 1979-09-28 1982-10-19 Nippon Electric Co., Ltd. Radio transmitter/receiver for digital and analog communications system
US4379947A (en) * 1979-02-02 1983-04-12 Teleprompter Corporation System for transmitting data simultaneously with audio

Family Cites Families (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4512013A (en) * 1983-04-11 1985-04-16 At&T Bell Laboratories Simultaneous transmission of speech and data over an analog channel

Patent Citations (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3718767A (en) * 1971-05-20 1973-02-27 Itt Multiplex out-of-band signaling system
US3875339A (en) * 1972-09-05 1975-04-01 I I Communications Inc Variable bandwidth voice and data telephone communication system
US3824347A (en) * 1973-02-01 1974-07-16 Ii Communications Corp Voice and data multiplexing system with improved signalling
US4238849A (en) * 1977-12-22 1980-12-09 International Standard Electric Corporation Method of and system for transmitting two different messages on a carrier wave over a single transmission channel of predetermined bandwidth
US4346380A (en) * 1978-12-11 1982-08-24 National Semiconductor Corporation Simultaneous communication of analog and binary information in a single frame of a pulse count modulated digital signal
US4280020A (en) * 1979-01-09 1981-07-21 Essex County Council Radio telephone system with direct digital carrier modulation for data transmission
US4379947A (en) * 1979-02-02 1983-04-12 Teleprompter Corporation System for transmitting data simultaneously with audio
US4355401A (en) * 1979-09-28 1982-10-19 Nippon Electric Co., Ltd. Radio transmitter/receiver for digital and analog communications system
US4313197A (en) * 1980-04-09 1982-01-26 Bell Telephone Laboratories, Incorporated Spread spectrum arrangement for (de)multiplexing speech signals and nonspeech signals

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
Conf. on Communications and Equipment and Systems, issued 04-07 April 1978, SHUM et al, A New Generation of Speech Plus Data Multiplexer, see pages 111-113 *
Telecommunications and Radio Engineering, issued July 1976, Vol. 30/31, BUKHUINER, Speech and Data Transmission in ACS Telephone Channels, see pages 111-113. *

Cited By (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0138988A1 (en) * 1983-04-11 1985-05-02 American Telephone & Telegraph Simultaneous transmission of speech and data over an analog channel.
EP0138988A4 (en) * 1983-04-11 1988-04-11 American Telephone & Telegraph Simultaneous transmission of speech and data over an analog channel.
EP0689337A1 (en) * 1994-06-20 1995-12-27 AT&T Corp. A method for dial-in access security using a multimedia modem
US5636282A (en) * 1994-06-20 1997-06-03 Paradyne Corporation Method for dial-in access security using a multimedia modem
US9118527B2 (en) 2012-10-09 2015-08-25 Fairchild Semiconductor Corporation Data during analog audio

Also Published As

Publication number Publication date
EP0138975A1 (en) 1985-05-02
EP0138975A4 (en) 1988-03-30
IT1176002B (en) 1987-08-12
IT8420477A0 (en) 1984-04-10
JPS60501086A (en) 1985-07-11
CA1203030A (en) 1986-04-08

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