US2859417A - Microwave filters - Google Patents

Microwave filters Download PDF

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Publication number
US2859417A
US2859417A US324545A US32454552A US2859417A US 2859417 A US2859417 A US 2859417A US 324545 A US324545 A US 324545A US 32454552 A US32454552 A US 32454552A US 2859417 A US2859417 A US 2859417A
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Prior art keywords
conductor
line
sections
conductors
gap
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US324545A
Inventor
Arditi Maurice
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TDK Micronas GmbH
International Telephone and Telegraph Corp
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Deutsche ITT Industries GmbH
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Priority to BE519797D priority Critical patent/BE519797A/xx
Priority to BE527584D priority patent/BE527584A/xx
Priority to BE518176D priority patent/BE518176A/xx
Priority to BE533239D priority patent/BE533239A/xx
Priority claimed from US286762A external-priority patent/US2794174A/en
Priority to US286765A priority patent/US2833995A/en
Priority to US286761A priority patent/US2820206A/en
Application filed by Deutsche ITT Industries GmbH filed Critical Deutsche ITT Industries GmbH
Priority to US324545A priority patent/US2859417A/en
Priority to GB2013/53A priority patent/GB726067A/en
Priority to FR1072220D priority patent/FR1072220A/en
Priority to US344748A priority patent/US2868966A/en
Priority to GB12114/53A priority patent/GB761765A/en
Priority to GB12111/53A priority patent/GB761762A/en
Priority to GB12110/53A priority patent/GB761761A/en
Priority to FR65725D priority patent/FR65725E/en
Priority to FR65726D priority patent/FR65726E/fr
Priority to CH317717D priority patent/CH317717A/en
Priority to CH316574D priority patent/CH316574A/en
Priority to FR65729D priority patent/FR65729E/fr
Priority to FR66218D priority patent/FR66218E/en
Priority to DEI7225A priority patent/DE1042048B/en
Priority to DEI7223A priority patent/DE1036950B/en
Priority to US383777A priority patent/US2822525A/en
Priority to GB31592/53A priority patent/GB765465A/en
Priority to GB31595/53A priority patent/GB761778A/en
Priority to FR66158D priority patent/FR66158E/en
Priority to FR66221D priority patent/FR66221E/en
Priority to GB8111/54A priority patent/GB749337A/en
Priority to DEI8435A priority patent/DE1002828B/en
Priority to FR66225D priority patent/FR66225E/en
Priority to CH328921D priority patent/CH328921A/en
Priority to FR66227D priority patent/FR66227E/en
Priority to FR67464D priority patent/FR67464E/en
Priority to FR68805D priority patent/FR68805E/en
Priority to US466753A priority patent/US2874276A/en
Priority to FR68853D priority patent/FR68853E/en
Priority to FR69008D priority patent/FR69008E/en
Priority to FR69959D priority patent/FR69959E/en
Priority to CH347233D priority patent/CH347233A/en
Priority to FR70420D priority patent/FR70420E/en
Priority to GB14706/56A priority patent/GB809482A/en
Publication of US2859417A publication Critical patent/US2859417A/en
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    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03L—AUTOMATIC CONTROL, STARTING, SYNCHRONISATION, OR STABILISATION OF GENERATORS OF ELECTRONIC OSCILLATIONS OR PULSES
    • H03L7/00—Automatic control of frequency or phase; Synchronisation
    • H03L7/02—Automatic control of frequency or phase; Synchronisation using a frequency discriminator comprising a passive frequency-determining element
    • H03L7/04—Automatic control of frequency or phase; Synchronisation using a frequency discriminator comprising a passive frequency-determining element wherein the frequency-determining element comprises distributed inductance and capacitance
    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B07—SEPARATING SOLIDS FROM SOLIDS; SORTING
    • B07C—POSTAL SORTING; SORTING INDIVIDUAL ARTICLES, OR BULK MATERIAL FIT TO BE SORTED PIECE-MEAL, e.g. BY PICKING
    • B07C3/00—Sorting according to destination
    • B07C3/003—Destination control; Electro-mechanical or electro- magnetic delay memories
    • B07C3/006—Electric or electronic control circuits, e.g. delay lines
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/18—Phase-shifters
    • H01P1/184—Strip line phase-shifters
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/201—Filters for transverse electromagnetic waves
    • H01P1/203—Strip line filters
    • H01P1/20327—Electromagnetic interstage coupling
    • H01P1/20354—Non-comb or non-interdigital filters
    • H01P1/20363—Linear resonators
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/201—Filters for transverse electromagnetic waves
    • H01P1/203—Strip line filters
    • H01P1/20327—Electromagnetic interstage coupling
    • H01P1/20354—Non-comb or non-interdigital filters
    • H01P1/20381—Special shape resonators
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/207—Hollow waveguide filters
    • H01P1/209—Hollow waveguide filters comprising one or more branching arms or cavities wholly outside the main waveguide
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P3/00—Waveguides; Transmission lines of the waveguide type
    • H01P3/02—Waveguides; Transmission lines of the waveguide type with two longitudinal conductors
    • H01P3/08—Microstrips; Strip lines
    • H01P3/085—Triplate lines
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/02—Coupling devices of the waveguide type with invariable factor of coupling
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/08—Coupling devices of the waveguide type for linking dissimilar lines or devices
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/08—Coupling devices of the waveguide type for linking dissimilar lines or devices
    • H01P5/10—Coupling devices of the waveguide type for linking dissimilar lines or devices for coupling balanced with unbalanced lines or devices
    • H01P5/107—Hollow-waveguide/strip-line transitions
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/12—Coupling devices having more than two ports
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/12—Coupling devices having more than two ports
    • H01P5/16—Conjugate devices, i.e. devices having at least one port decoupled from one other port
    • H01P5/18—Conjugate devices, i.e. devices having at least one port decoupled from one other port consisting of two coupled guides, e.g. directional couplers
    • H01P5/184—Conjugate devices, i.e. devices having at least one port decoupled from one other port consisting of two coupled guides, e.g. directional couplers the guides being strip lines or microstrips
    • H01P5/187—Broadside coupled lines
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/12—Supports; Mounting means
    • H01Q1/22—Supports; Mounting means by structural association with other equipment or articles
    • H01Q1/24—Supports; Mounting means by structural association with other equipment or articles with receiving set
    • H01Q1/247—Supports; Mounting means by structural association with other equipment or articles with receiving set with frequency mixer, e.g. for direct satellite reception or Doppler radar
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/06—Details
    • H01Q9/065—Microstrip dipole antennas

Definitions

  • This invention relates to microwave transmission systems and more particularly to microwave filters specially applicable to microwave printed transmlssion lines and circuitry.
  • filter arrangements are disclosed utilizing a section of the aforementioned parallel strip type of line.
  • spaced susceptances are provided in the form of conductor obstacles projecting either partway or all the way across the space between the parallel strip conductors.
  • spaced susceptances are provided by two obstacles or other discontinuity structures in or on one or the other or both of the conductors of the line at spaced points to forma resonant section therebetween.
  • An object of this invention is to provide still other microwave filter and susceptance arrangements which are small, light in weight, and relatively simple .and inexpensive to make, also utilizing conductor elements or sections of the aforementioned parallel conductor type of line.
  • One of the features of this invention is the manner of providing spaced .susceptances of large value by making gaps in certain of the conductors of a parallel strip type of line.
  • the gap susceptances may comprise various shapes widths and angles, and may include gaps between spaced overlapping conductors or spaces between adjacent conductors of the same or different cross-sectional configurations.
  • Another important aspect of the invention is that the gap susceptance permits D. C. isolation between the different sections of the line conductor.
  • Fig. 3 is a graph showing the magnitude of the equiva- 2,859,417 Patented Nov. 4, '1958 ice lent shunt susceptances with the referenceplane taken along line AB of Fig. 1;
  • Fig. 4 is a plan view of an alternate form of-filter;
  • Fig. .5 is a cross-sectional view taken along line 5- -5 of Fig. 4;
  • Figs. 6 and 7 are plan viewsof other .embodimentsof the invention.
  • Fig. 8 is a graph showing values, of the. ratio Power input Power output versus gaps spacing for theembodiment shown-inFig. 6 wherein the line on both sides of the gap are matched;
  • Fig. 9 is a plan view of still another embodiment of the invention.
  • Fig. 10 is a graph showing frequencyresponse curves for filter configurations according to Fig. 1, 6 and 9;
  • Fig. 11 is a longitudinal cross-sectionalview .of still another embodiment of the invention.
  • Figs. 12. and 13 are plan views o'fIstill other alternatives of filter configurations according to the present invention.
  • the microwave. transmission line shown is of the printed circuittype comprising a first or line conductor 1 and a second .or' base conductorZ with a layer of dielectric material3 therebetween.
  • the conductive, material may be applied and/or shaped or etchedon a layer of dielectric materiaLsuch as polystyrene, polyethylene, quartz, Tefion, Fiberglas or other suitable material of high dielectric quality in accordance with known printed circuit techniques.
  • the spacing of the two conductors is preferably selected a small fraction of a quarter wavelength of the microwave propagated therealong, asuitable fraction being in the order of one-tenth to one-fifth of a quarter wavelength.
  • the vfilter comprises a length of base conductor 2,v a layer of dielectric 3, and several resonant sections of line conductor, such as indicated at 4,5 and. 6, quarter .wave
  • .susceptances is determined largely by thelength of the line conductor therebetween, reference in this regard being made to the equivalent circuit shown in Fig. 3.
  • Resonant sections 4, 5 and 6 each comprises approximately a half wavelength or amultiple thereof, the resonant sections being coupled by other sections of line, such as 4a and 5a, approximately one quarter wavelength or a odd multiple thereof, as may be desired.
  • the magnitude of the susceptance depends on the gap Width and also on the angle of the gap with respect to the longitudinal axis of the line conductor.
  • the V-shaped gaps 7 provide for larger R.-F. coupling as compared to a truly transverse gap, such as indicated in Figs. 6 and 7.
  • the width of the gaps is important and should be maintained small depending on the configuration of the adjacent .end portions of the conductor sections.
  • the angle on (Fig. 1') has also an important bearing on the value of the susceptance.
  • Fig. 3 the equivalent circuit elements are given as a function of the angle a with respect to the longitudinal axis of the line conductor, Fig. l.
  • the values illustrated by curve 8 of Fig. 3 were obtained with a gap width of one millimeter, a line conductor 1 of six millimeters width, a conductor 2 of twenty-six millimeter width and a dielectric spacing between conductor. 1 and 2 of '1.5
  • the line conductor 11 is shown to be broken up into sections as indicated at 9 and 10, wherein the ends of successive sections are directly coupled by V-shaped gaps 11a, 11b and 110.
  • the gaps 11a and 110 are small in width and present relatively small values of susceptance while gap 11b is much larger in width and
  • theconductors 1a and 2a are shown to be of equal width and, as an example, this width may be five millimeters. while the dielectric may be six millimeters in width.
  • the gaps may be provided in either of the two con- "ductors or alternate therebetween, it being more practical,
  • Figs. 6 and 7 show two embodiments of the invention, one in which the narrow line conductor is made in sections and in the other, where the wider base conductor is made into sections.
  • the line conductor 10 is shown tocomprise resonant sections 12 and 13, quarter wave coupled by a quarter wave section 14.
  • the gap susceptances 15 are disposed transverse to the longitudinal axis of the line conductor.
  • a thin layer of dielectric material 30 maintains the conductors in spaced relation.
  • Fig. 7 the line conductor 10 is made continuous while the ground conductor 2c is provided with gaps 16 at spaced points thus forming a resonant section 17 therebetween, this resonant section being approximately onehalf wavelength between susceptances although a multiple thereof will suffice where desired, the same as in connection with the other embodiments herein disclosed. It
  • gaps 15 and 16 may be varied in width in accordance with the susceptance values and the type of coupling desired.
  • the curve 18 shown in Fig. 8 illustrates the transmission property through a gap 15 of line conductor of the type shown in Fig. 6.
  • the test data for this curve was taken from a susceptance gap of the configuration shown in Fig. 6, wherein the line conductor was six millimeters wide, the base conductor 2c was twenty-six millimeters wide and the spacing therebetween was 1.5 millimeters.
  • the values for the curve were obtained by varying the width of the gap between 1 and millimeters.
  • resonant sections 19 and 20 are shown of line conductor material approximately one half wavelength electrically between reference planes X and Y of the associated gaps, coupled by approximately quarter wavelength sections, as indicated at 21, the sections being disposed in lapped spaced relationship in a plane parallel to the ground conductor 22.
  • the line sections are supported on the ground conductor by a thin layer of dielectric material 23.
  • the gaps 24 and 25 may be varied both in width and length in accordance with the susceptance value desired. In this connection, it should be recognized that the length of the sections 19,
  • Sections 19, 21 therefore are not truly half wavelength nor is coupling section 20a quarter wavelength.
  • Curve 26 corresponds to a filter of the configuration illustrated in Fig. 1, wherein the angle on of the V- shaped gap is 35 degrees, the other dimensions being in accordance with those given for the curve illustrated in Fig. 3, that is, the line conductor was six millimeters wide, the ground conductor twenty-six millimeters wide and the dielectric thickness was 1.5 millimeters.
  • Curve 27 corresponds to a filter configuration in accordance with the form illustrated in Fig.
  • the base or ground conductor 2c is shown to be wider than the line conductor 1c and to underlie throughout the resonant sections formed d limeter in width and the gap at the other end of the section was .75 millimeter in width.
  • the dimensions of the conductors and the dielectric layer were otherwise the same as those of the filter from which curve 26 was derived.
  • Curve 28 corresponds to a filter section in accordance with the embodiment illustrated in Fig. 9, the length of the section corresponding to section 19 being fifty-four millimeters long, the width of the gap being 0.2 millimeter and the length of the gap being eighteen millimeters.
  • the line conductor was six millimeters wide and the ground conductor was twenty-six millimeters wide.
  • the dielectric material employed in all three specimens was Fiberglas.
  • the lapped relationship may be in a plane normal to the plane of the conductors.
  • a resonant section is shown in Fig. 11.
  • the ends of the line conductors 29 and 30 are spaced apart and a line section 31 is spaced thereabove in overlapping relation as shown.
  • the resonant section between the reference planes X and Y is approximately one half wavelength electrically.
  • the gaps 32 where the section 31 overlies the end portions of the line conductor may be controlled as desired by the thickness of the dielectric layer 33.
  • the dielectric layer 33 may be integral with the dielectric layer 34 between the line conductor and the ground conductor 35 or it may be separate therefrom, whichever is desired.
  • the dielectric layer 33 may also correspond to the layer 34 in thickness, the susceptance value in that case being adjusted by varying the amount of overlap between the end portions of the conductors 29 and 31, for example.
  • Fig. 12 shows alternate sections 36 and 37 of different width whereby the end portions of the wider section is disposed in spaced relation to the end portion of the narrower section.
  • Fig. 13 a similar arrangement is shown except that the end portion of the larger section 38 is recessed at 39 to receive in spaced relation thereto the end portion 40 of the smaller section 41.
  • This latter form is similar to the form illustrated in Fig. 1 with respect to the lapped male-female relationship of the adjacent end portions of the line conductors.
  • the resonant sections of the various embodiments may be tuned by any of the methods disclosed in the aforesaid applications Serial Nos. 286,761, now Patent No. 2,820,- 206, and 286,763, new Patent No. 2,819,452.
  • a microwave bandpass filter comprising a ribbonlike line conductor, a ribbon-like ground conductor, dielectric means'disposing said conductors in spaced substantially parallel relation a small fraction of wavelength apart, said line conductor being divided into distinct lengths, adjacent lengths of said line conductor being spaced apart to form susceptance gaps and the conductor length between certain adjacent gaps being of a size such that the parallel conductors thereof constitute a resonant section, the terminating ends of adjacent conductors being disposed in overlapping spaced relation with the gap between adjacent conductor lengths being small with negligible capacitive effect but suflicient to establish an electromagnetic field bulging laterally with respect to said gap, thereby presenting a discontinuity in the propagation path of microwave energy along said conductors.
  • a microwave bandpass filter according to claim 1 wherein the overlapping terminations of adjacent conductor portions are angularly disposed to present a gap disposed at an acute angle to the longitudinal axis of said line conductor.
  • a microwave bandpass filter according to claim 1 wherein the overlapping terminations of the adjacent portions of said line conductor comprise conductor lengths disposed in oifset overlapping relation in a common plane parallel to the plane of said ground conductor, said ground conductor being disposed in underlying relation to said conductor portions.
  • a microwave bandpass filter according to claim 1 wherein two of said conductor lengths lie in the same plane parallel to the plane of said ground conductor and a third conductor length lies in another plane parallel to the planes of said two conductors in spaced overlapping relation with the terminations of said two conductors.
  • a microwave bandpass filter according to claim 1 wherein the overlapping relation between two adjacent conductor lengths comprises a recess in one of said lengths and a projection for the other of said lengths received in spaced relation in said recess.

Description

Nov. 4, 1958 M. ARDlTl 2,859,417
MICROWAVE FILTERS Filed Dec. 6, 1952 4 Sheets-Sheet 1 A 8 3 6 A m 3; 5 APPROXIMATE p 0 2 Q EQUIVALENT I 5 u; CIRCUIT J 9. t 5 NEGLECTING Lossss sue m m/v05 5 I l l l I l l I I a lo 4o a0 c //Y DEGREES la lla 9 #5 +5" INVENTOR MAURICE ARD/T/ BY v 3? ATTORNEY NQV. 4, 1958 MARDITI v 2,859,417
' MICROWAVE FILTERS I 4 Sheets-Sheet 2-- Filed Dec. 6,1952
Am w
' INVENTOR Y MAUR/LE ARDITI.
Q BY fiAP WIDTH/N MILLIMETER5 f7 ATTORNEY 1'0 1 wk I Nov. 4, 1958 M. ARDlTl MICROWAVE FILTERS 4 Sheets-Sheet 4 Filed Dec. 6, 1952 $2 \S smut 8% 8% 93v 8? Q3 gms INVENTO MAURICE ARD/T/ ATTORNEY MICRUWAVE FILTERS Maurice Arditi,.lifton, N. J., assignor to International Telephoneand Telegraph Corporation, a corporation of Maryland Application December 1952, Serial No. 324,545
v5 Claims. (Cl. 333-73) This invention relates to microwave transmission systems and more particularly to microwave filters specially applicable to microwave printed transmlssion lines and circuitry.
In the copending applications of D. D. Grieg and H. F. Engelmann, Serial Nos. 227,896, now abandoned, and 234,503,11ow Patent No. 2,721,312, filed May 23,1951, and June 30, 1951, respectively, and M. Arditi and P. Parzen, Serial No. 286,764, filed May 8, 1952, now Patent No. 2,- 774,046, a type of microwave transmission line is disclosed comprising, in one of its simplest forms, two conductors printed or otherwise disposed in substantially parallel relation on opposite sides of a strip or layer of dielectric material a small fraction of a quarter wavelength thick. The two conductors may be the same width or one may be made wider than the other. In the copending applications of M. Arditi, G. A. Deschamps and J. Elefant, Serial No. 286,761, filed May 8, 1952, now Patent No. 2,820,206, and Serial No. 286,763, filed May 8, 1952, now Patent No. 2,819,452, filter arrangements are disclosed utilizing a section of the aforementioned parallel strip type of line. In one, spaced susceptances are provided in the form of conductor obstacles projecting either partway or all the way across the space between the parallel strip conductors. In the other, spaced susceptances are provided by two obstacles or other discontinuity structures in or on one or the other or both of the conductors of the line at spaced points to forma resonant section therebetween.
An object of this invention is to provide still other microwave filter and susceptance arrangements which are small, light in weight, and relatively simple .and inexpensive to make, also utilizing conductor elements or sections of the aforementioned parallel conductor type of line.
, One of the features of this invention is the manner of providing spaced .susceptances of large value by making gaps in certain of the conductors of a parallel strip type of line. The gap susceptances may comprise various shapes widths and angles, and may include gaps between spaced overlapping conductors or spaces between adjacent conductors of the same or different cross-sectional configurations. Another important aspect of the invention is that the gap susceptance permits D. C. isolation between the different sections of the line conductor.
of Fig. 1;
Fig. 3,is a graph showing the magnitude of the equiva- 2,859,417 Patented Nov. 4, '1958 ice lent shunt susceptances with the referenceplane taken along line AB of Fig. 1; Fig. 4 is a plan view of an alternate form of-filter; Fig. .5 is a cross-sectional view taken along line 5- -5 of Fig. 4;
Figs. 6 and 7 are plan viewsof other .embodimentsof the invention;
Fig. 8 is a graph showing values, of the. ratio Power input Power output versus gaps spacing for theembodiment shown-inFig. 6 wherein the line on both sides of the gap are matched;
Fig. 9 is a plan view of still another embodiment of the invention;
Fig. 10 is a graph showing frequencyresponse curves for filter configurations according to Fig. 1, 6 and 9;
Fig. 11 is a longitudinal cross-sectionalview .of still another embodiment of the invention; and
Figs. 12. and 13 are plan views o'fIstill other alternatives of filter configurations according to the present invention.
Referringto Figs. 1 and 2 the microwave. transmission line shown is of the printed circuittype comprising a first or line conductor 1 and a second .or' base conductorZ with a layer of dielectric material3 therebetween. The conductive, material may be applied and/or shaped or etchedon a layer of dielectric materiaLsuch as polystyrene, polyethylene, quartz, Tefion, Fiberglas or other suitable material of high dielectric quality in accordance with known printed circuit techniques. The spacing of the two conductors is preferably selected a small fraction of a quarter wavelength of the microwave propagated therealong, asuitable fraction being in the order of one-tenth to one-fifth of a quarter wavelength.
The vfilter comprises a length of base conductor 2,v a layer of dielectric 3, and several resonant sections of line conductor, such as indicated at 4,5 and. 6, quarter .wave
.susceptances is determined largely by thelength of the line conductor therebetween, reference in this regard being made to the equivalent circuit shown in Fig. 3. Resonant sections 4, 5 and 6 each comprises approximately a half wavelength or amultiple thereof, the resonant sections being coupled by other sections of line, such as 4a and 5a, approximately one quarter wavelength or a odd multiple thereof, as may be desired. The magnitude of the susceptance depends on the gap Width and also on the angle of the gap with respect to the longitudinal axis of the line conductor.
It will be clear to those skilled in the art that alternate gaps may be arranged at different angles and/ or dilferent widths and in different directions. The V-shaped gaps 7 provide for larger R.-F. coupling as compared toa truly transverse gap, such as indicated in Figs. 6 and 7. The width of the gaps is important and should be maintained small depending on the configuration of the adjacent .end portions of the conductor sections. The angle on (Fig. 1') has also an important bearing on the value of the susceptance. In Fig. 3 the equivalent circuit elements are given as a function of the angle a with respect to the longitudinal axis of the line conductor, Fig. l. The values illustrated by curve 8 of Fig. 3 were obtained with a gap width of one millimeter, a line conductor 1 of six millimeters width, a conductor 2 of twenty-six millimeter width and a dielectric spacing between conductor. 1 and 2 of '1.5
presentsa relatively large susceptance.
millimeters, wherein the dielectric employed was Fiberglas.
In Figs. 4 and 5, the line conductor 11: is shown to be broken up into sections as indicated at 9 and 10, wherein the ends of successive sections are directly coupled by V-shaped gaps 11a, 11b and 110. The gaps 11a and 110 are small in width and present relatively small values of susceptance while gap 11b is much larger in width and In this embodiment, theconductors 1a and 2a are shown to be of equal width and, as an example, this width may be five millimeters. while the dielectric may be six millimeters in width. Whether or not the conductors are made of the same width, the gaps may be provided in either of the two con- "ductors or alternate therebetween, it being more practical,
however, to make the gaps in the narrower of the two where they are of unequal widths.
Figs. 6 and 7 show two embodiments of the invention, one in which the narrow line conductor is made in sections and in the other, where the wider base conductor is made into sections. In Fig. 6, for example, the line conductor 10 is shown tocomprise resonant sections 12 and 13, quarter wave coupled by a quarter wave section 14. The gap susceptances 15 are disposed transverse to the longitudinal axis of the line conductor.
of the line conductor. A thin layer of dielectric material 30 maintains the conductors in spaced relation.
In Fig. 7 the line conductor 10 is made continuous while the ground conductor 2c is provided with gaps 16 at spaced points thus forming a resonant section 17 therebetween, this resonant section being approximately onehalf wavelength between susceptances although a multiple thereof will suffice where desired, the same as in connection with the other embodiments herein disclosed. It
should also be recognized that the gaps 15 and 16 may be varied in width in accordance with the susceptance values and the type of coupling desired.
' The curve 18 shown in Fig. 8 illustrates the transmission property through a gap 15 of line conductor of the type shown in Fig. 6. The test data for this curve was taken from a susceptance gap of the configuration shown in Fig. 6, wherein the line conductor was six millimeters wide, the base conductor 2c was twenty-six millimeters wide and the spacing therebetween was 1.5 millimeters. The values for the curve were obtained by varying the width of the gap between 1 and millimeters.
In the embodiment shown in Fig. 9, resonant sections 19 and 20 are shown of line conductor material approximately one half wavelength electrically between reference planes X and Y of the associated gaps, coupled by approximately quarter wavelength sections, as indicated at 21, the sections being disposed in lapped spaced relationship in a plane parallel to the ground conductor 22. The line sections are supported on the ground conductor by a thin layer of dielectric material 23. The gaps 24 and 25 may be varied both in width and length in accordance with the susceptance value desired. In this connection, it should be recognized that the length of the sections 19,
20 and 21 may be varied considerably depending upon the width and length of the gaps 24 and 25. Sections 19, 21 therefore are not truly half wavelength nor is coupling section 20a quarter wavelength.
The three frequency response curves of Fig. 10 illustrate the pass band characteristics of the filters herein disclosed. Curve 26 corresponds to a filter of the configuration illustrated in Fig. 1, wherein the angle on of the V- shaped gap is 35 degrees, the other dimensions being in accordance with those given for the curve illustrated in Fig. 3, that is, the line conductor was six millimeters wide, the ground conductor twenty-six millimeters wide and the dielectric thickness was 1.5 millimeters. Curve 27 corresponds to a filter configuration in accordance with the form illustrated in Fig. 6 with the exception that the gap at one end of the resonant section was one-tenth mil- The base or ground conductor 2c is shown to be wider than the line conductor 1c and to underlie throughout the resonant sections formed d limeter in width and the gap at the other end of the section was .75 millimeter in width. The dimensions of the conductors and the dielectric layer were otherwise the same as those of the filter from which curve 26 was derived. Curve 28 corresponds to a filter section in accordance with the embodiment illustrated in Fig. 9, the length of the section corresponding to section 19 being fifty-four millimeters long, the width of the gap being 0.2 millimeter and the length of the gap being eighteen millimeters. The line conductor was six millimeters wide and the ground conductor was twenty-six millimeters wide. The dielectric material employed in all three specimens was Fiberglas.
Instead of the lapped spaced relationship, such as indicated for sections 19 and 20 in Fig. 9, being in a plane parallel to the line or ground conductor, the lapped relationship may be in a plane normal to the plane of the conductors. Such a resonant section is shown in Fig. 11. The ends of the line conductors 29 and 30 are spaced apart and a line section 31 is spaced thereabove in overlapping relation as shown. The resonant section between the reference planes X and Y is approximately one half wavelength electrically. The gaps 32 where the section 31 overlies the end portions of the line conductor may be controlled as desired by the thickness of the dielectric layer 33. The dielectric layer 33 may be integral with the dielectric layer 34 between the line conductor and the ground conductor 35 or it may be separate therefrom, whichever is desired. The dielectric layer 33 may also correspond to the layer 34 in thickness, the susceptance value in that case being adjusted by varying the amount of overlap between the end portions of the conductors 29 and 31, for example.
Many variations of the gap configuration between adjacent sections of the line conductor are possible and as further illustrated, Fig. 12 shows alternate sections 36 and 37 of different width whereby the end portions of the wider section is disposed in spaced relation to the end portion of the narrower section. In Fig. 13 a similar arrangement is shown except that the end portion of the larger section 38 is recessed at 39 to receive in spaced relation thereto the end portion 40 of the smaller section 41. This latter form, of course, is similar to the form illustrated in Fig. 1 with respect to the lapped male-female relationship of the adjacent end portions of the line conductors.
The resonant sections of the various embodiments may be tuned by any of the methods disclosed in the aforesaid applications Serial Nos. 286,761, now Patent No. 2,820,- 206, and 286,763, new Patent No. 2,819,452.
While I have described above the principles of my invention in connection with specific apparatus, it is to be clearly understood that this description is made only by way of example and not as a limitation to the scope of my invention as set forth in the objects thereof and in the accompanying claims.
I claim:
1. A microwave bandpass filter comprising a ribbonlike line conductor, a ribbon-like ground conductor, dielectric means'disposing said conductors in spaced substantially parallel relation a small fraction of wavelength apart, said line conductor being divided into distinct lengths, adjacent lengths of said line conductor being spaced apart to form susceptance gaps and the conductor length between certain adjacent gaps being of a size such that the parallel conductors thereof constitute a resonant section, the terminating ends of adjacent conductors being disposed in overlapping spaced relation with the gap between adjacent conductor lengths being small with negligible capacitive effect but suflicient to establish an electromagnetic field bulging laterally with respect to said gap, thereby presenting a discontinuity in the propagation path of microwave energy along said conductors.
2. A microwave bandpass filter according to claim 1 wherein the overlapping terminations of adjacent conductor portions are angularly disposed to present a gap disposed at an acute angle to the longitudinal axis of said line conductor.
3. A microwave bandpass filter according to claim 1 wherein the overlapping terminations of the adjacent portions of said line conductor comprise conductor lengths disposed in oifset overlapping relation in a common plane parallel to the plane of said ground conductor, said ground conductor being disposed in underlying relation to said conductor portions.
4. A microwave bandpass filter according to claim 1 wherein two of said conductor lengths lie in the same plane parallel to the plane of said ground conductor and a third conductor length lies in another plane parallel to the planes of said two conductors in spaced overlapping relation with the terminations of said two conductors.
5. A microwave bandpass filter according to claim 1 wherein the overlapping relation between two adjacent conductor lengths comprises a recess in one of said lengths and a projection for the other of said lengths received in spaced relation in said recess.
References Cited in the file of this patent UNITED STATES PATENTS 2,274,346 Roosenstein Feb. 24, 1942 2,402,540 Espley June 25, 1946 2,411,555 Rogers Nov. 26, 1946 2,721,312 Grieg et a1 Oct. 18, 1955 2,760,169 Engelrnann Aug. 21, 1956 FOREIGN PATENTS 655,803 Great Britain Aug. 1, 1951
US324545A 1952-05-08 1952-12-06 Microwave filters Expired - Lifetime US2859417A (en)

Priority Applications (40)

Application Number Priority Date Filing Date Title
BE519797D BE519797A (en) 1952-05-08
BE527584D BE527584A (en) 1952-05-08
BE518176D BE518176A (en) 1952-05-08
BE533239D BE533239A (en) 1952-05-08
US286765A US2833995A (en) 1952-05-08 1952-05-08 Microwave transmission line
US286761A US2820206A (en) 1952-05-08 1952-05-08 Microwave filters
US324545A US2859417A (en) 1952-05-08 1952-12-06 Microwave filters
GB2013/53A GB726067A (en) 1952-05-08 1953-01-23 Microwave coupling arrangements
FR1072220D FR1072220A (en) 1952-05-08 1953-03-05 High frequency transmission systems and in particular coupling device
US344748A US2868966A (en) 1952-05-08 1953-03-26 Radio frequency radio receiver with line-above-ground directional couplers and automatic frequency control
GB12114/53A GB761765A (en) 1952-05-08 1953-05-01 Microwave transmission line
GB12111/53A GB761762A (en) 1952-05-08 1953-05-01 Microwave transmission systems and impedance matching devices therefor
GB12110/53A GB761761A (en) 1952-05-08 1953-05-01 Microwave filters
FR65725D FR65725E (en) 1952-05-08 1953-05-04 High frequency transmission systems and in particular coupling device
FR65726D FR65726E (en) 1952-05-08 1953-05-04
CH317717D CH317717A (en) 1952-05-08 1953-05-06 Ultra-shortwave transmission line
CH316574D CH316574A (en) 1952-05-08 1953-05-06 Ultra shortwave transmission line
FR65729D FR65729E (en) 1952-05-08 1953-05-06
FR66218D FR66218E (en) 1952-05-08 1953-05-06 High frequency transmission systems and in particular coupling device
DEI7223A DE1036950B (en) 1952-05-08 1953-05-07 Arrangement for the compensation of joints on a microwave ribbon cable by means of a reactance
DEI7225A DE1042048B (en) 1952-05-08 1953-05-07 Arrangement for changing the electrical length of a line section of a microwave ribbon line
US383777A US2822525A (en) 1952-05-08 1953-10-02 High frequency hybrid circuit
GB31592/53A GB765465A (en) 1952-05-08 1953-11-13 Improvements in or relating to radio wave guide systems
GB31595/53A GB761778A (en) 1952-05-08 1953-11-13 Microwave filters
FR66158D FR66158E (en) 1952-05-08 1953-12-01 High frequency transmission system and in particular coupling device
FR66221D FR66221E (en) 1952-05-08 1953-12-01 High frequency transmission system and in particular coupling device
GB8111/54A GB749337A (en) 1952-05-08 1954-03-19 Radio frequency circuits
DEI8435A DE1002828B (en) 1952-05-08 1954-03-23 Directional coupler in the microwave range for asymmetrical ribbon cables
FR66225D FR66225E (en) 1952-05-08 1954-03-24 High frequency transmission systems and in particular coupling devices
CH328921D CH328921A (en) 1952-05-08 1954-03-25 High frequency coupling device
FR66227D FR66227E (en) 1952-05-08 1954-03-26 High frequency transmission systems and in particular coupling device
FR67464D FR67464E (en) 1952-05-08 1954-07-20 High frequency transmission system and in particular coupling device
FR68805D FR68805E (en) 1952-05-08 1954-10-01 High frequency transmission systems and in particular coupling device
US466753A US2874276A (en) 1952-05-08 1954-11-04 Unitary antenna-receiver utilizing microstrip conductors
FR68853D FR68853E (en) 1952-05-08 1954-11-12 High frequency transmission systems and in particular coupling device
FR69008D FR69008E (en) 1952-05-08 1955-01-07 High frequency transmission system and in particular coupling device
FR69959D FR69959E (en) 1952-05-08 1956-02-17 High frequency transmission systems and in particular coupling device
CH347233D CH347233A (en) 1952-05-08 1956-05-01 Microwave transmission line
FR70420D FR70420E (en) 1952-05-08 1956-05-11 High frequency transmission system and in particular coupling device
GB14706/56A GB809482A (en) 1952-05-08 1956-05-11 Microwave lines and high q filters

Applications Claiming Priority (4)

Application Number Priority Date Filing Date Title
US286762A US2794174A (en) 1952-05-08 1952-05-08 Microwave transmission systems and impedance matching devices therefor
US324545A US2859417A (en) 1952-05-08 1952-12-06 Microwave filters
US749337XA 1953-03-26 1953-03-26
US3159253A 1953-11-13 1953-11-13

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US466753A Expired - Lifetime US2874276A (en) 1952-05-08 1954-11-04 Unitary antenna-receiver utilizing microstrip conductors

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US466753A Expired - Lifetime US2874276A (en) 1952-05-08 1954-11-04 Unitary antenna-receiver utilizing microstrip conductors

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BE (4) BE527584A (en)
CH (4) CH316574A (en)
DE (3) DE1036950B (en)
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GB (7) GB726067A (en)

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Publication number Priority date Publication date Assignee Title
US2954468A (en) * 1958-03-25 1960-09-27 Thompson Ramo Wooldridge Inc Microwave filter and detector
US2976498A (en) * 1959-08-03 1961-03-21 Electronic Specialty Co Radio frequency filter
US3104362A (en) * 1959-08-27 1963-09-17 Thompson Ramo Wooldridge Inc Microwave filter
US3111634A (en) * 1960-05-13 1963-11-19 Singer Inc H R B Strip transmission line modulator
US3156880A (en) * 1960-08-04 1964-11-10 Melpar Inc Lumped constant filter
US3345589A (en) * 1962-12-14 1967-10-03 Bell Telephone Labor Inc Transmission line type microwave filter
US3518583A (en) * 1965-09-30 1970-06-30 Fujitsu Ltd Broad range frequency selective ultra-high frequency impedance device
US3548344A (en) * 1967-07-28 1970-12-15 Varian Associates Stripline gain equalizer
US3605045A (en) * 1969-01-15 1971-09-14 Us Navy Wide-band strip line frequency-selective circuit
US3688225A (en) * 1969-05-21 1972-08-29 Us Army Slot-line
US3668569A (en) * 1970-05-27 1972-06-06 Hazeltine Corp Distributed-constant dispersive network
US3909755A (en) * 1974-07-18 1975-09-30 Us Army Low pass microwave filter
EP0068345A1 (en) * 1981-06-25 1983-01-05 Communications Satellite Corporation Symmetrical coupled line coplanar waveguide filter
US5334961A (en) * 1991-08-12 1994-08-02 Matsushita Electric Industrial Co., Ltd. Strip-line type bandpass filter
EP1098384A2 (en) * 1999-11-05 2001-05-09 Murata Manufacturing Co., Ltd. Dielectric filter, dielectric duplexer, and communication apparatus
EP1098384A3 (en) * 1999-11-05 2002-05-15 Murata Manufacturing Co., Ltd. Dielectric filter, dielectric duplexer, and communication apparatus
US6535079B1 (en) 1999-11-05 2003-03-18 Murata Manufacturing Co., Ltd. Dielectric filter, dielectric duplexer, and communication apparatus
WO2007100324A1 (en) * 2006-03-01 2007-09-07 Lucent Technologies Inc. Meta-material filter for use in a base station of a wireless communications system

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GB761761A (en) 1956-11-21
BE533239A (en)
GB761778A (en) 1956-11-21
GB726067A (en) 1955-03-16
GB749337A (en) 1956-05-23
FR66221E (en) 1956-06-05
FR68805E (en) 1958-06-10
GB761762A (en) 1956-11-21
US2874276A (en) 1959-02-17
CH317717A (en) 1956-11-30
DE1036950B (en) 1958-08-21
FR69008E (en) 1958-08-27
FR66218E (en) 1956-06-05
DE1042048B (en) 1958-10-30
CH328921A (en) 1958-03-31
CH347233A (en) 1960-06-30
FR65725E (en) 1956-03-12
FR66227E (en) 1956-06-05
CH316574A (en) 1956-10-15
BE519797A (en)
FR68853E (en) 1958-06-11
FR69959E (en) 1959-01-30
FR65726E (en) 1956-03-12
BE527584A (en)
FR70420E (en) 1959-05-06
FR1072220A (en) 1954-09-09
DE1002828B (en) 1957-02-21
FR65729E (en) 1956-03-12
FR66225E (en) 1956-06-05
GB761765A (en) 1956-11-21
GB809482A (en) 1959-02-25
BE518176A (en)

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