CN1142445C - 电池测试装置 - Google Patents
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Abstract
本发明提供一种用于测试或者监测蓄电池工作状态的设备。本发明的一个方面是在电池测试装置中采用一个Kelvin探测器用电感抵消电路,这种电感抵消电路降低在所述Kelvin探测器的探头之间的电感耦合。该设备还包括一个DC耦合AC的放大器,用于放大电池测试装置的AC响应信号。本发明的其他方面还包括临界阻尼带通滤波器、DC-DC变换器隔离电路、操作员可编程测试标准、电池温度传感元件和一个自动调节增益级,并且采用一个自校准的内部基准。
Description
技术领域
本发明涉及蓄电池的测试技术,特别是,本发明涉及用于测试蓄电池的电池测试装置。
背景技术
蓄电池已经存在很久了,例如广泛应用在机动车或需要辅助电源的工业领域的铅酸蓄电池。人们始终在致力于了解这种蓄电池的特性、研究蓄电池是如何工作的,特别是致力于精确测试蓄电池的状态,但是,事实证明,这种努力还远没有达到令人满意的程度。蓄电池包括多个在电气上串联连接的蓄电池单元,每个蓄电池单元的电压大约是2.1V,通过串联连接这些蓄电池单元,它们的电压将叠加构成一个总的电压。例如,以典型的机动车蓄电池为例,通过六个蓄电池单元的串联连接,形成一个总的电压,当蓄电池满充电时,这个电压为12.6V。
多年来,人们一直致力于能够精确测试出蓄电池的状态。一种简单的测试方式是测量蓄电池的电压,如果所测量的电压低于某个确定的门限值,就认为此电池是坏的。可是,这种测量方式并不方便,因为它要求在测量之前必须先给蓄电池充电,如果蓄电池被放电,其上的电压必然降低,则好电池也会被认为是坏的。此外,这种测量不是显示出蓄电池内还存有多少能量。另一种测试技术是将蓄电池测试视为一种负载测试。在一个负载测试中,用一个已知负载将电池放电,当电池放电时,监测电池两端的电压,从而确定该电池当时的状态。这种测量技术要求电池必须被充分充电,以便能够向负载提供电流。
近来,由Illinois的Burr Ridge公司的Keith S.Champlin和Midtronics博士首创了一种通过测量电池的导电率来测试蓄电池的方法,这种方法的有关教导可在多篇美国专利文献中看到,例如1975年3月25日公开的Champlin的专利US-3,873,911,题目为“电池测试装置”;1975年9月30日公开的Champlin的专利US-3,909,708,题目为“电池测试装置”;1989年3月28日公开的Champlin的专利US-4,816,768,题目为“电池测试装置”;1989年4月25日公开的Champlin的专利US-4,825,170,题目为“带有自动电压扫描的电池测试装置”;1989年11月14日公开的Champlin的专利US-4,881,038,题目为“带有自动电压扫描可以确定其动态状态的电池测试装置”;1990年3月27日公开的Champlin的专利US-4,912,416,题目为“带有充电状态补偿的电池测试装置”;1992年8月18日公开的Champlin的专利US-5,140,269,题目为“用于鉴定电池/电池单元蓄电量的电池测试装置”;1994年8月30日公开的专利US-5,343,380,题目为“在电池充电和放电时抑制时间变化信号的方法和设备”;1996年11月5日公开的专利US-5,572,136,题目为“带有用于低充电状态自动补偿器的电池测试装置”;1996年12月12日公开的专利US-5,574,355,题目为“在电池充电时监测和控制热失控的方法和设备”;1996年12月17日公开的专利US-5,585,728,题目为“带有用于低充电状态自动补偿器的电池测试装置”;1997年1月7日公开的专利US-5,592,093,题目为“通过比较电路检测松散端子连接的电池测试装置”;1997年1月28日公开的专利US-5,598,098,题目为“带有抗强噪声功能的电池测试装置”;1998年5月26日公开的专利US-5,757,192,题目为“在蓄电池中检测坏电池单元的方法和设备”;1998年10月13日公开的专利US-5,821,756,题目为“带有低充电状态特制自动补偿器的电池测试装置”;1998年11月3日公开的专利US-5,831,435,题目为“适用于日本工业标准的电池测试装置”。
发明内容
本发明包括电池测试或蓄电池工作状态监测的设备和方法。本发明的一个措施是在电池测试装置中采用一个Kelvin探测器用电感抵消电路,这种电感抵消电路降低在所述Kelvin探测器的探头之间的电感耦合。本发明的另一个措施是包括一个DC耦合AC的放大器,用于放大电池测试装置的AC响应信号。本发明的其他措施还包括临界阻尼带通滤波器、DC-DC变换器隔离电路、操作员可编程测试标准、电池温度传感元件和一个自动调节增益级,并且采用一个自校准的内部基准。
附图说明
图1是表示本发明的电池测试装置的简化方框图;
图2是采用Kelvin探测器的本发明的电感抵消电路的示意图;
图3是图1的DC耦合AC放大器的简化示意图;
图4A是图1的临界阻尼滤波器的一级的简化示意图;
图4B是代表图4A的滤波器的响应信号的幅值和频率曲线;
图5是图1的可以调节增益放大器的简化示意图;
图6是根据本发明又一方案的DC-DC变换器的简化方框图;
图7是根据本发明又一方案的断路电路的简化电路图;
图8是根据本发明又一方案的自校准标准化电路的简化电路图。
具体实施方式
目前仍然存在改进蓄电池测试技术的要求,为此本发明致力于提供一种电池测试装置,测试时电流可流入或流出电池(即一个电流交换器),所述电流按照工频交流频率交变,本发明使用一个大阻抗的负载,其优点包括:
·具有抗接触阻抗变化的特性,
·高容量一能够用单个电路无损坏地测试1-6个电池单元,
·用于连接电池的探测导线具有稳定的和/或可预测的电流耦合效应,
根据公式G(导电率)=I/E,其中I表示一个基本上固定不变的电流,因此只有变量E需要测量,而且它与G在数量上成简单的倒数关系,
可减少装置中电保险的数量。
图1是电池检测装置10的简化方框图,说明根据本发明的一个方案监测蓄电池12的状态的检测装置的实施例。这种电池检测装置10通过一个由电缆16A、16B、18A和18B连接的电感抵消电路20和自校准电路21共同形成的四点Kelvin电路连接电池12的两个端子14A和14B。可开闭的电流源22包括一个开关22A和与电缆18A及18B串联连接的电流源22B。在一个实施例中,开关22A工作在5HZ和500HZ。根据本发明的一个措施,电缆16A和16B与高阻抗的DC耦合AC放大器24相连接。根据本发明的又一个措施,这个DC耦合AC放大器24提供一个放大的输出26到一个临界阻尼滤波器28,后者输出一个经过滤波的信号30到一个自调节放大器32。从自调节放大器32输出的信号34送到模/数变换器36,后者的输出信号38继而送到微处理器40,微处理器与一个显示输出装置42和一个键控器、键盘或其他输入装置44相连接。如图所示的其他输入和输出装置I/O 46也可以连接到微处理器40上。例如,微处理器40可以连接到外部打印机设备、数据通信设备一调制解调器,或外部存贮设备,I/O 46的连接可以采用物理连接或通过非物理的连接实现,例如通过远红外、超声波或无线电频率。根据本发明,电池测试装置10由DC-DC变换器48供电。
图2是简化的电感抵消电路20的电路图,该电路通过一个Kelvin连接将电池12与电流源22和DC耦合AC放大器24相连接,现有技术的电池测试装置的一个问题是由于Kelvin连接常常与电池相连接而引起互感,这导致在传感探头中电流的电感耦合干扰,因为这些探头距离很近。然而采用本发明如图所示的变压器耦合连接,能够有效地避免上述不希望的交叉耦合干扰。因此本发明可允许使用多芯、可更换的电缆,而且可适用大容量的电池。变压器50的线圈52和54分别与Kelvin导线16B和18B串联连接,变压器线圈52和54按相反方向缠绕在铁芯56上。
在导线18B和18A中流动的电流来自电流源22,它们感应耦合到导线16B和16A。在已有的电池测试装置中,上述现象可能是导致测量误差的根源。但是,变压器50在导线16B和16A中耦合产生一个相反的起抵消作用的电流。在线圈52和54之间的耦合可以通过调节铁芯56的位置得到控制,在制造变压器时可以实现这种调节。另外,电缆16A、16B、18A和18B与电池测试装置10的连接可以是可拆卸的连接方式,如果电缆被损坏,或者由于其他原因需要更换电缆,很容易实现新电缆对的安装。新电缆对包括其自己的变压器50,该变压器在制造时已经通过调节铁芯56实现了“调谐”,因此能够排除干扰电流。应注意在不太临界的应用情况下,可以使用固定的变压器成品,变压器耦合无需调谐。而且,电感抵消电路20的使用允许电缆长度较长,而不会在电缆之间出现电感过度耦合现象。例如,电缆测试电路可以与电池隔开一段距离,由操作员在操作台或坐在机动车内进行测试操作。可以变换长度不一或结构不同的各种电缆,只需简单地将电缆对从测试装置10上拆下,再连接上新更换的电缆对。如果电缆事先已经进行了适当的抵消性调谐,操作员无需再作任何进一步调节。图2所示的变压器只是这种概念的一个简单实施例,还可以采用其他产生抵消信号的技术,例如通过有源设备或其他未超出本发明原理的技术。
图3是根据本发明的又一实施例的DC耦合AC放大器的简化示意图,这种DC耦合AC放大器24包括差分放大器60和差分放大器62。在图3所示的实施例中,放大器60的非倒相输入端通过一个电阻64如图1所示连接到电缆16A,放大器60的倒相输入端通过如图2所示的线圈52和电阻66连接到电缆16B。放大器60的输出端通过电阻68连接到放大器60的倒相输入端,以便提供负反馈。放大器60的输出端通过电阻72和74及积分电路70连接到放大器60的非倒相输入端。逆变器70是这样构成的,差分放大器62的输出端通过一个电容器76负反馈连接到其倒相输入端,差分放大器62的非倒相输入端则接地。在一个优选的实施例中,这种DC耦合AC放大器24具有一个整体增益。
在现有技术中,电池测试装置普遍采用AC耦合的放大器,但是这种放大器产生公共模式误差,以及由于用于耦连感应信号的电容器的变化,其阻抗是变化的。此外,要求耦合电容器的电容量要大,从而避免破坏输入的感应信号,这种电容器的存在对于获得准确的测量结果所必须的设定时间的减少具有负面效应。然而,在现有技术的电池测试装置中采用AC耦合可以避免电池的DC电压由于放大器的高增益而导致倍压。采用DC耦合AC放大器能够克服上述缺陷,并且无需大的耦合电容器。
在如图所示的实施例中,DC耦合AC放大器24接收来自放大器60的输出端的代表DC信号的DC误差信号80,这个DC误差信号80由积分电路70产生,后者的时间常数由电容器76决定,电容量的选择根据用于开关电流源22的开关22A的工作频率的应用情况而定。因此,DC耦合AC放大器24的输出26是响应开关的电流源22的应用而产生的纯交流信号。图3所示的图例只是本发明的一个具体实施例,表示根据本发明的一个DC耦合AC放大器的优选实施例。需要说明的是,本发明包括用于从被测试电池感应交流信号的任何耦合技术,这种技术无需安装用于截止电池的DC电压的大的AC耦合电容器。
图4A是图1所示的临界阻尼滤波器28的第二级滤波级200的简化电路图,图4B是表示根据本发明的滤波器28的特性的频率-幅值曲线图。在优选的实施例中,滤波器28包括四个这样的级100,级100包括一个通过电阻102个电容器104实现负反馈的差分放大器110,其输入信号通过电阻106和电容器108连接到放大器110的倒相输入端,放大器110的非倒相输入端通过电阻112接地78。
滤波器100形成带通滤波器的第二级,并且用作图1所示的临界阻尼滤波器28的一个信号级。临界阻尼滤波器28包括四个相互串连连接的级共同构成。
临界阻尼滤波器28提供一个如图4B所示的临界阻尼带通滤波器,图4B也示出了一个过阻尼滤波器和一个欠阻尼滤波器的曲线。滤波器28最好具有Q等于1,其带通中心频率(F0)应与图1所示的开关22A的频率相同。如果该滤波器是过阻尼的,系统的响应会较慢,如果滤波器是欠阻尼的,系统的信号将“响”,这样将基本上只允许电池12上的在响应信号中的成份能够通过自调整放大器30,电池12的频率与电流源22相同。注意也可以使用超出优选实施例的附加的滤波器级,例如八个级,不过这将增加制造成本。在一个优选实施例中,放大器28的总增益为16。任何种类的滤波器均可以应用在本发明中,图中所示的一个简单的优选的实施例是专用模拟滤波器,然而还可以使用数字式滤波器。
图5是自调整放大器(可编程增益或可选择增益)32的简化的电路图。在图5所示的实施例中,放大器32是个两级放大器,其第一级140具有可选择增益1、2、4和8,第二级放大器142具有可选择增益1、10、100和1000。放大器140通过耦合电容器144连接到临界阻尼滤波器28的输出端30。放大器140包括可选择增益放大器146和电阻148。放大器146接收由放大器146进行放大控制的输入信号A0和A1,放大器级142包括放大器150,其输入端通过电阻152和耦合电容器154连接到放大器146的输出端,放大器150的增益受输入信号A2和A3控制,放大器146和150通过控制输入A0-A3连接到微处理机40,微处理机40根据下表通过选择改变输入信号A0-A3来控制放大器32的增益:表1
A3 | A2 | A1 | A0 | 增益 | A3 | A2 | A1 | A0 | 增益 |
0 | 0 | 0 | 0 | 1 | 1 | 0 | 0 | 0 | 100 |
0 | 0 | 0 | 1 | 2 | 1 | 0 | 0 | 1 | 200 |
0 | 0 | 1 | 0 | 4 | 1 | 0 | 1 | 0 | 400 |
0 | 0 | 1 | 1 | 8 | 1 | 0 | 1 | 1 | 800 |
0 | 1 | 0 | 0 | 10 | 1 | 1 | 0 | 0 | 1000 |
0 | 1 | 0 | 1 | 20 | 1 | 1 | 0 | 1 | 2000 |
0 | 1 | 1 | 0 | 40 | 1 | 1 | 1 | 0 | 4000 |
0 | 1 | 1 | 1 | 80 | 1 | 1 | 1 | 1 | 8000 |
在工作期间,放大器32提供一个在1和8000之间的可编程的增益,在微处理机40的控制下,放大器32的增益是可以调整的,因此电池测试装置10能够在很宽的电阻或电导范围内测试电池(即在10欧姆-10000欧姆之间)。微处理机40通过控制输入信号A0-A3直到接收到通过模/数变换器36的最大信号为止,增加放大器32的增益。这种调整的实现是自动完成的,无需由操作员干预。这证明可以很容易地使用装置10,并且可以减少由于操作员的失误产生的不准确测量的可能性。图5中所示的可调增益放大器32是一个简单的可调节放大器,本发明可以使用任何放大器结构。而且,放大器可以放置在信号通道的任何位置上,并非必须放置在例如滤波器28的临界阻尼滤波器和模/数变换器36之间。
图6是根据本发明的又一实施方案的DC-DC变换器电路48的简化的示意图。电路48包括开关型DC-DC变换器170,它包括正极和负极输入端、正极和负极输出端及一个同步输入端。图6的DC-DC变换器的电压用VCC,V′CC,+VSS和-VSS表示,其中VCC或者由一个内部电压源如内部蓄电池提供,或者如果电池12容量足够大,由该电池供给。VCC连接到变换器170的正极输入端,V′CC通过电阻172连接到变换器170的正极输入端,电容器174连接VCC接地78,电容器176连接V′CC接地78。电阻172和电容器174的组合和电阻172和电容器176的组合为滤波器提供在V′CC和VCC上的信号噪声。在本发明的一个实施例中,VCC用于驱动非常低的噪声电路,例如放大器24,滤波器28,放大器32等等。但是,V′CC用于驱动可以产生噪声的电源电路,其本身对于噪声极不敏感,这种电源电路例如微处理机40和其他数字和逻辑电路。电压+VSS和-VSS用于向某些要求多电源的模拟器件供电,例如正和负15V。电感178和180阻塞来自变换器170的噪声,变换器由+VSS和-VSS供电。在一个实施例中,变换器170是一个开关变换器,其频率大约为400KHZ,微处理机40的工作频率大约在4MHZ,图6的实施例中提供的噪声隔离功能降低了电池测试装置10的临界器件的噪声,从而改善了测量精度。
变换器170还包括功率减少技术,由微处理机40提供的信号包括同步自动协调(SYNCIN)。在这种情况下,模拟测试电路无需工作。在这些时间周期内,微处理机40可以控制所述SYNCIN到变换器170,使变换器170截止,不产生电压供给+VSS和-VSS,如此可以减少功率需求。
本发明的另一方案能够改善内部(电源)电池寿命。本发明可以被用于测试电池,利用内部电池的1.75V电压作为开路电压(如果电池12的容量足够大,装置10可由电池12供电)。如果认为可充电电池装置太贵,也可用活动便携的9V电池作为内部电池。这种电池能够提供比较低的蓄电能,因为本发明是由多个只需要较小功率的电路构成,因此延长了电池的寿命。这些电路包括双级模拟功率关闭电路200(图7),使测试时间最小的高速尖峰-低谷(TOP-DOWN)自调整电路和一个电源48的自动功率下降电路(如上所述)。
在一个实施例中,放大器32在1-8000之间自动调整,如果是相互衔接的,放大器32消耗所述内部电池的功率是不相互衔接情况的10倍,因此,其优点是限制了该放大器的接通时间。因为串连阻抗的累积作用,增加电池单元的数量可以使电导率降低,结果,低电导率测量需要的增益比高电导率测量的情况低得多。
特别是,电池12的电池单元数量可以由微处理机40得知,它已经由操作员输入微处理机,微处理机40据此控制测量所需的放大器32的初始增益。根据初始增益,微处理机可以调整放大器的增益上升或者下降,从而获得特定电池结构的适当的增益,这样可大大降低获得测量数据所需的时间量,减少功率消耗。在一个实施例中,放大器32的初始增益选择如下:
电池数量
初始增益
1 8000
2 4000
3 4000
4 2000
5 1000
6 800
关闭电路200如图7所示,可以用于断开所有供给装置10中的模拟电路的电源,这种电路包括内部电池202,晶体管204和206,二极管208和偏置电阻210、212、214和216。如果装置10连接到电池12,晶体管204导通,依次激励晶体管206,于是电压内部电池202的VDD供给电路200的输出端,这个电压VDD供给装置10中模拟器件功率。但是,如果摘掉电池12,晶体管204将截止,于是终止电压VDD的供给。在运行中,微处理机40可以通过由二极管208提供的信号使晶体管206截止来选择性终止电压VDD的供给。因此本发明的一个方案包括断开某些器件的连接,这些器件不使用由装置10的内部电池202供给的内部电源。实现本发明的这个方案的多个技术采用一个简化的实施例表示,本领域的一般技术人员在这个实施例的启发下,能够使用其他类似技术终止对各种器件的功率供给或者关闭各种器件。
本发明的又一个方案是使用校准电路21实现自校准,该电路如图8所示,电路21包括锰铜镍合金分路导线标准240,分路240可以按照NIST标准被校准,开关240、242和244连接到微处理机40,并且与选择性开关分路240相适配,后者与一个放大器24串连连接。微处理机利用放大器24、滤波器28、放大器32和模/数变换器36测量出分路240的电导率,将测量值与读取的已经存在微处理机40的存储器40A内的校准标准相比较,根据上述测量值和校准值之间的差,产生一个校准系数,并且连续测量,维持电池测试装置10的自校准。如果测试装置10开始连接到电池12上,或者由用户通过键盘44开始连接到电池上,这种校准可以自动产生。
在本发明的又一方案中,微处理机40的存储器48包括各种预定的参考标准。由操作员通过输入装置44选择适当的用于特定电池12的参考标准,不过操作员也可以调出已经存入存储器40A中的标准,并且展示在显示器42上,如果标准已经改变,或者希望修改标准,操作员可以利用键盘输入装置改变所述标准,已经存入存储器40A的标准也可以打印出来,例如使用输入/输出端口46。
采用自动温度补偿器是本发明的另一个特征。图1中所示的温度传感器250可以向微处理机40输入一个温度信号,例如,传感器250包括一个热电耦、热敏电阻或者一个直接朝向电池12的红外温度传感器。一个模/数变换器(未示出)向微处理机40提供一个温度信号250的数字符,根据测量的温度,微处理机40根据存入存储器40A中的信息校准测试结果,从而补偿温度的变化。
本发明已经参照上述多个实施例进行了说明,本领域的一般技术人员据此所作出的形式和细节上的变化均未脱离本发明的原理和范围。采用任何适当的技术可以实现图1所示的各个电路的功能,并不局限于这里的说明。而且,本发明的各种方案的实现没有特定的顺序,也不局限于图1所示的顺序。这些电路功能既可以用模拟电路实现,也可以用数字电路实现,或者二者的混合体实现。而且,电流源22B可以利用开关22A选择性开关操作,本发明也包括电压的应用和测量合成电流响应。本发明可以用于电池测试电路有关的导电率、导纳、阻抗或电阻的测量。此外,本发明的某些方案可以应用在任何形式的电池测试装置上,包括负载测试装置、简单电压测试装置和需要通过许多条件步骤安放电池的测试装置等。
Claims (16)
1.一种监测蓄电池工作状态的装置,包括:
电子电池测试电路,它通过一个第一KELVIN连接和第二KELVIN连接与蓄电池相互连接;
连接到所述电池测试电路的第一端子的第一和第二电导线,其设置成连接到电池的第一KELVIN连接;
连接到所述电池测试装置的第二端子的第三和第四电导线,其设置成连接到电池的第二KELVIN连接;以及
感应抵消电路连接第一电导线到第二电导线。
2.根据权利要求1的装置,其中所述感应抵消电路在第二导线中提供一个反向的电流,作为第一导线中的电流的函数。
3.根据权利要求2的装置,其中在第一导线中的电流包含电源电流,第二电导线提供连接到所述电池测试电路的电压传感连接。
4.根据权利要求3的装置,其中第一导线传送的电信号频率在5HZ和500HZ之间。
5.根据权利要求1的装置,其中感应抵消电路是一个变压器。
6.根据权利要求5的装置,其中变压器的第一线圈与第一导线串联连接,变压器的第二线圈与第二导线串联连接。
7.根据权利要求6的装置,其中所述第一和第二线圈的极性相反。
8.根据权利要求1的装置,其中所述抵消电路包括在第二导线中提供一个作为第一导线中电流的函数的反向电流的电路。
9.根据权利要求1的装置,其中在第一导线中的第一传感电流流入第三导线,作为第二传感电流,并且感应抵消电路连接第二传感电流到第二导线。
10.根据权利要求1的装置,其中第一导线与第二导线相邻敷设。
11.根据权利要求1的装置,其中第一、第二、第三和第四导线可拆下地连接到电池测试电路中,所述感应抵消电路安放在这样一个壳体内,其内安装有第一、第二、第三和第四导线,使感应抵消电路在制造时与不同规格的导线相互匹配连接。
12.根据权利要求1的装置,其中第一、第二、第三和第四导线具有足够的长度,使电池测试装置安装在机动车内部,所述导线能够伸到位于机动车发动机室中的蓄电池处。
13.一种降低在电池测试装置的KELVIN探测器中的感应耦合电流的方法,包括:
所述KELVIN探测器与在第一导线内流动的传感电流相耦连;及
相应于所述传感电流在KELVIN探测器的第二导线中提供一个相反的电流,这个相反的电流与在第二导线中流动的感应耦合电流流动方向相反。
14.根据权利要求13的方法,其中耦连的步骤包括使传感电流直接流入一个变压器的第一线圈,和将变压器的第二线圈与所述第二导线串联连接的步骤。
15.根据权利要求14的方法,包括调节所述与传感电流反向的电流以便消除所述感应耦合电流的步骤。
16.根据权利要求15的方法,其中调节步骤包括调节在变压器的第一和第二线圈之间的耦合状态。
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US09/264,743 US6172505B1 (en) | 1998-04-27 | 1999-03-09 | Electronic battery tester |
US09/264,743 | 1999-03-09 |
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CN1142445C true CN1142445C (zh) | 2004-03-17 |
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-
1999
- 1999-03-09 US US09/264,743 patent/US6172505B1/en not_active Expired - Lifetime
- 1999-03-18 CN CNB991059476A patent/CN1142445C/zh not_active Expired - Lifetime
- 1999-04-12 WO PCT/US1999/007895 patent/WO1999056121A1/en active IP Right Grant
- 1999-04-12 AU AU35534/99A patent/AU3553499A/en not_active Abandoned
- 1999-04-12 DE DE69933553T patent/DE69933553T2/de not_active Expired - Lifetime
- 1999-04-12 JP JP2000546231A patent/JP2003502792A/ja active Pending
- 1999-04-12 EP EP99917402A patent/EP1075655B1/en not_active Expired - Lifetime
-
2000
- 2000-05-26 HK HK00103141A patent/HK1024058A1/xx unknown
Also Published As
Publication number | Publication date |
---|---|
JP2003502792A (ja) | 2003-01-21 |
DE69933553T2 (de) | 2007-06-28 |
AU3553499A (en) | 1999-11-16 |
CN1236894A (zh) | 1999-12-01 |
DE69933553D1 (de) | 2006-11-23 |
US6172505B1 (en) | 2001-01-09 |
EP1075655B1 (en) | 2006-10-11 |
EP1075655A4 (en) | 2004-10-27 |
EP1075655A1 (en) | 2001-02-14 |
WO1999056121A1 (en) | 1999-11-04 |
HK1024058A1 (en) | 2000-09-29 |
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