CA2405794A1 - Waveguide-finline tunable phase shifter - Google Patents
Waveguide-finline tunable phase shifter Download PDFInfo
- Publication number
- CA2405794A1 CA2405794A1 CA002405794A CA2405794A CA2405794A1 CA 2405794 A1 CA2405794 A1 CA 2405794A1 CA 002405794 A CA002405794 A CA 002405794A CA 2405794 A CA2405794 A CA 2405794A CA 2405794 A1 CA2405794 A1 CA 2405794A1
- Authority
- CA
- Canada
- Prior art keywords
- tunable
- phase shifter
- waveguide
- shifter according
- dielectric layer
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Abandoned
Links
Classifications
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P1/00—Auxiliary devices
- H01P1/18—Phase-shifters
- H01P1/181—Phase-shifters using ferroelectric devices
Abstract
A tunable phase shifter includes a waveguide, a finline substrate positioned within the waveguide, a tunable dielectric layer positioned on the finline substrate, a first conductor positioned on the tunable dielectric layer, and a second conductor positioned on the tunable dielectric layer, with the first and second conductors being separated to form a gap. By controlling a voltag e applied to the tunable dielectric material, the phase of a signal passing through the waveguide can be controlled.
Description
WAVEGUIDE-FINLINE TUNABLE PHASE SHIFTER
CROSS REFERENCE TO RELATED APPLICATION
This application claims the benefit of the filing date of United States Provisional Application No. 60/198,690, filed April 20, 2000.
FIELD OF INVENTION
The present invention relates to electronic waveguide devices and more particularly to waveguide-finlines used to control the phase of a guided signal.
BACKGROUND OF INVENTION
Modern communications systems are using increasingly higher frequencies.
At high frequencies, communications utilize higher data transmit/receive rates. When steerable array antennas are used in high frequency communications systems, it is desirable for each antenna element to have fast scan capabilities, small size, low cost and reasonable performance. Phase shifters are critical components for meeting those criteria.
Electronic phase shifters are used in many devices to delay the transmission of an electric signal. Waveguide phase shifters have been described in United States Patents No. 4,982,171 and 4,654,611. United States Patent No. 4,320,404 discloses a phase shifter using diode switches connected to wire conductors inside a waveguide that are turned on or off to cause a phase shift of the propagating wave. United States Patents No.
4,434,409; 4, 532, 704; 4,818,963; 4,837,528; 5,724,011 and 5,811,830 disclose tuning ferrites, ferromagnetic or ferroelectric slab materials inside waveguides to achieve phase shifting.
United States Patents No.. 4,894,627; 4,789,840 and 4,782,346 disclose devices that use finline structures to build couplers, signal detectors and radiating antennas.
These patents either use slab material in a waveguide to construct phase shifters or use fmlines for some other application.
Tunable ferroelectric materials are materials whose pennittivity (more commonly called dielectric constant) can be varied by varying the strength of an electric field to which the materials are subjected. Even though these materials work in their paraelectric phase above the Curie temperature, they are conveniently called "ferroelectric"
because they exhibit spontaneous polarization at temperatures below the Curie temperature.
CROSS REFERENCE TO RELATED APPLICATION
This application claims the benefit of the filing date of United States Provisional Application No. 60/198,690, filed April 20, 2000.
FIELD OF INVENTION
The present invention relates to electronic waveguide devices and more particularly to waveguide-finlines used to control the phase of a guided signal.
BACKGROUND OF INVENTION
Modern communications systems are using increasingly higher frequencies.
At high frequencies, communications utilize higher data transmit/receive rates. When steerable array antennas are used in high frequency communications systems, it is desirable for each antenna element to have fast scan capabilities, small size, low cost and reasonable performance. Phase shifters are critical components for meeting those criteria.
Electronic phase shifters are used in many devices to delay the transmission of an electric signal. Waveguide phase shifters have been described in United States Patents No. 4,982,171 and 4,654,611. United States Patent No. 4,320,404 discloses a phase shifter using diode switches connected to wire conductors inside a waveguide that are turned on or off to cause a phase shift of the propagating wave. United States Patents No.
4,434,409; 4, 532, 704; 4,818,963; 4,837,528; 5,724,011 and 5,811,830 disclose tuning ferrites, ferromagnetic or ferroelectric slab materials inside waveguides to achieve phase shifting.
United States Patents No.. 4,894,627; 4,789,840 and 4,782,346 disclose devices that use finline structures to build couplers, signal detectors and radiating antennas.
These patents either use slab material in a waveguide to construct phase shifters or use fmlines for some other application.
Tunable ferroelectric materials are materials whose pennittivity (more commonly called dielectric constant) can be varied by varying the strength of an electric field to which the materials are subjected. Even though these materials work in their paraelectric phase above the Curie temperature, they are conveniently called "ferroelectric"
because they exhibit spontaneous polarization at temperatures below the Curie temperature.
Tunable ferroelectric materials including barium-strontium titanate (BST) or BST
composites have been the subject of several patents.
Dielectric materials including baxium strontium titanate are disclosed in U.S.
Patent No. 5,312,790 to Sengupta, et al. entitled "Ceramic Ferroelectric Material"; U.S.
Patent No. 5,427,988 to Sengupta, et al. entitled "Ceramic Ferroelectric Composite Material-BSTO-Mg0"; U.S. Patent No. 5,486,491 to Sengupta, et al. entitled "Ceramic Ferroelectric Composite Material - BSTO-Zr02' ; U.S. Patent No. 5,635,434 to Sengupta, et al. entitled "Ceramic Ferroelectric Composite Material-BSTO-Magnesium Based Compound"; U.S. Patent No. 5,830,591 to Sengupta, et al. entitled "Multilayered Ferroelectric Composite Waveguides"; U.S. Patent No. 5,846,893 to Sengupta, et al.
entitled "Thin Film Ferroelectric Composites and Method of Making"; U.S.
Patent No.
5,766,697 to Sengupta, et al. entitled "Method of Making Thin Film Composites"; U.S.
Patent No. 5,693,429 to Sengupta, et al. entitled "Electronically Graded Multilayer Ferroelectric Composites"; and U.S. Patent No. 5,635,433 to Sengupta, entitled "Ceramic Fenoelectric Composite Material-BSTO-Zn0". These patents are hereby incorporated by reference. Copending, commonly assigned United States patent application Serial No.
09/594,837 titled "Electronically Tunable Ceramic Materials Including Tunable Dielectric And Metal Silicate Phases", filed June 15, 2000, and Serial No. 09/768,690 titled "Electronically Tunable Low-Loss Ceramic Materials Including a Tunable Dielectric Phase and Multiple Metal Oxide Phases", filed January 24, 2001, disclose additional tunable dielectric materials and are also incorporated by reference. The materials shown in these patents exhibit low dielectric loss and high tunability. Tunability is defined as the fractional change in the dielectric constant with applied voltage.
United States Patents No. 5,355,104 and 5,724,011 disclose phase shifters that include voltage controllable dielectric materials.
The prior art does not disclose a finline waveguide structure that is used as a tunable phase shifter. There is a need for tunable phase shifters that are relatively simple in structure, low in cost, and can be rapidly controlled.
SUMMARY OF THE INVENTION
Tunable phase shifters constructed in accordance with this invention include a waveguide, a finline substrate positioned within the waveguide, a tunable dielectric layer positioned on the fmline substrate, a first conductor positioned on the tunable dielectric layer, and a second conductor positioned on the voltage tunable dielectric layer, with the first and second conductors being separated to form a gap.
By controlling the voltage applied to the conductors, the phase of a signal passing through the waveguide can be controlled.
BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 is an exploded isometric view of a tunable phase shifter constructed in accordance with a first embodiment of the invention;
FIG. 2 is a side elevation view of a fmline structure the may be used in the phase slufter of FIG. 1;
FIG. 3 is a cross-sectional view of the finline of FIG. 2 taken along line 3-3;
FIG. 4 is a cross-sectional view of an assembled version of the waveguide phase shifter of FIG. 1 taken along line 4-4;
FIG. 5 is graph of the phase shift versus bias voltage for a phase shifter constructed in accordance with the invention;
FIG. 6 is graph of the losses versus bias voltage for a phase shifter constructed in accordance with the invention;
FIG. 7 is an exploded isometric view of another tunable phase shifter constructed in accordance with the invention;
FIG. 8 is a side elevation view of a fmline structure the may be used in the phase shifter of FIG. 7;
FIG. 9 is a cross-sectional view of the fmline of FIG. 8 taken along line 9-9;
FIG. 10 is an exploded isometric view of another tunable phase shifter constructed in accordance with the invention;
FIG. 11 is a side elevation view of a fmline structure the may be used in the phase shifter of FIG. 10; and FIG. 12 is a cross-sectional view of the finline of FIG. 11 taken along line 12-12.
DETAILED DESCRIPTION OF THE INVENTION
The invention provides a waveguide-finline tunable phase shifter that uses a film of voltage tunable material mounted on a finline. When a DC tuning voltage is applied to the tunable film, the dielectric constant of the film changes, which causes a change in the group velocity, and therefore, produces a phase shift in a signal passing through the waveguide.
Referring to the drawings, FIG. 1 is an exploded isometric view of a 30 GHz tunable phase shifter 10 constructed in accordance with a preferred embodiment of the invention. The phase shifter 10 includes a waveguide 12 including side portions 14 and 16.
In one embodiment, the waveguide can be a WR-28, 26 to 40 GHz rectangular waveguide.
However, the invention is not limited to a particular type of waveguide or frequency of operation. Side portion 14 includes a longitudinal groove 18 and side portion 16 includes a longitudinal groove 20. When the side portions are brought together, the grooves form a channel 22. First and second conductive plates 24 and 26 are positioned between the waveguide portions. Conductive plate 24 includes a connection point 28 for connection to a variable DC voltage source 30 by way of conductor 32. A finline structure 34 is positioned between the conductive plates, which in the preferred embodiment are made of copper.
Insulating sheets 36 and 38 are positioned on opposite sides of conductive plate 24 to insulate it from the conductive waveguide portions. In the preferred embodiment, the insulating sheets are made of mica. Conductive plate 26 is allowed to male electrical contact with the waveguide portions and is connected to an electrical ground either directly, or through the waveguide portions.
FIG. 2 is a side elevation view of a fmline structure 34 that may be used in the phase shifter of FIG. 1, and FIG. 3 is a cross-sectional view of the finline structure 34 talen along line 3-3. Finline structure 34 includes a low dielectric constant, low loss substrate 40 with a layer of tunable material 42 deposited thereon. The preferred embodiment of this invention utilizes Mg0 as the substrate material. The tunable material is metalized with conductive material to form electrodes 46 and 48 that define a gap 44, which separates the electrodes 46 and 48 on the tunable material layer. The gap extends longitudinally from a first end 50 to a second end 52 of the structure. The gap includes a central portion 54 and first and second exponentially tapered end portions 56 and 58 respectively. The end portions are tapered such that the gap widens near the ends to provide impedance matching. Referring to FIG. 1, conductive plates 24 and 26 form exponentially tapered gaps 60 and 62 to provide additional impedance matching. Gaps 60 and 62 lie adjacent to the ends of gap portions 56 and 58 respectively. A plurality of openings, for example 64, 66 and 68, are located in the various components of the phase shifter of FIG. 1 for receiving fasteners that will be used to hold the phase shifter together.
composites have been the subject of several patents.
Dielectric materials including baxium strontium titanate are disclosed in U.S.
Patent No. 5,312,790 to Sengupta, et al. entitled "Ceramic Ferroelectric Material"; U.S.
Patent No. 5,427,988 to Sengupta, et al. entitled "Ceramic Ferroelectric Composite Material-BSTO-Mg0"; U.S. Patent No. 5,486,491 to Sengupta, et al. entitled "Ceramic Ferroelectric Composite Material - BSTO-Zr02' ; U.S. Patent No. 5,635,434 to Sengupta, et al. entitled "Ceramic Ferroelectric Composite Material-BSTO-Magnesium Based Compound"; U.S. Patent No. 5,830,591 to Sengupta, et al. entitled "Multilayered Ferroelectric Composite Waveguides"; U.S. Patent No. 5,846,893 to Sengupta, et al.
entitled "Thin Film Ferroelectric Composites and Method of Making"; U.S.
Patent No.
5,766,697 to Sengupta, et al. entitled "Method of Making Thin Film Composites"; U.S.
Patent No. 5,693,429 to Sengupta, et al. entitled "Electronically Graded Multilayer Ferroelectric Composites"; and U.S. Patent No. 5,635,433 to Sengupta, entitled "Ceramic Fenoelectric Composite Material-BSTO-Zn0". These patents are hereby incorporated by reference. Copending, commonly assigned United States patent application Serial No.
09/594,837 titled "Electronically Tunable Ceramic Materials Including Tunable Dielectric And Metal Silicate Phases", filed June 15, 2000, and Serial No. 09/768,690 titled "Electronically Tunable Low-Loss Ceramic Materials Including a Tunable Dielectric Phase and Multiple Metal Oxide Phases", filed January 24, 2001, disclose additional tunable dielectric materials and are also incorporated by reference. The materials shown in these patents exhibit low dielectric loss and high tunability. Tunability is defined as the fractional change in the dielectric constant with applied voltage.
United States Patents No. 5,355,104 and 5,724,011 disclose phase shifters that include voltage controllable dielectric materials.
The prior art does not disclose a finline waveguide structure that is used as a tunable phase shifter. There is a need for tunable phase shifters that are relatively simple in structure, low in cost, and can be rapidly controlled.
SUMMARY OF THE INVENTION
Tunable phase shifters constructed in accordance with this invention include a waveguide, a finline substrate positioned within the waveguide, a tunable dielectric layer positioned on the fmline substrate, a first conductor positioned on the tunable dielectric layer, and a second conductor positioned on the voltage tunable dielectric layer, with the first and second conductors being separated to form a gap.
By controlling the voltage applied to the conductors, the phase of a signal passing through the waveguide can be controlled.
BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 is an exploded isometric view of a tunable phase shifter constructed in accordance with a first embodiment of the invention;
FIG. 2 is a side elevation view of a fmline structure the may be used in the phase slufter of FIG. 1;
FIG. 3 is a cross-sectional view of the finline of FIG. 2 taken along line 3-3;
FIG. 4 is a cross-sectional view of an assembled version of the waveguide phase shifter of FIG. 1 taken along line 4-4;
FIG. 5 is graph of the phase shift versus bias voltage for a phase shifter constructed in accordance with the invention;
FIG. 6 is graph of the losses versus bias voltage for a phase shifter constructed in accordance with the invention;
FIG. 7 is an exploded isometric view of another tunable phase shifter constructed in accordance with the invention;
FIG. 8 is a side elevation view of a fmline structure the may be used in the phase shifter of FIG. 7;
FIG. 9 is a cross-sectional view of the fmline of FIG. 8 taken along line 9-9;
FIG. 10 is an exploded isometric view of another tunable phase shifter constructed in accordance with the invention;
FIG. 11 is a side elevation view of a fmline structure the may be used in the phase shifter of FIG. 10; and FIG. 12 is a cross-sectional view of the finline of FIG. 11 taken along line 12-12.
DETAILED DESCRIPTION OF THE INVENTION
The invention provides a waveguide-finline tunable phase shifter that uses a film of voltage tunable material mounted on a finline. When a DC tuning voltage is applied to the tunable film, the dielectric constant of the film changes, which causes a change in the group velocity, and therefore, produces a phase shift in a signal passing through the waveguide.
Referring to the drawings, FIG. 1 is an exploded isometric view of a 30 GHz tunable phase shifter 10 constructed in accordance with a preferred embodiment of the invention. The phase shifter 10 includes a waveguide 12 including side portions 14 and 16.
In one embodiment, the waveguide can be a WR-28, 26 to 40 GHz rectangular waveguide.
However, the invention is not limited to a particular type of waveguide or frequency of operation. Side portion 14 includes a longitudinal groove 18 and side portion 16 includes a longitudinal groove 20. When the side portions are brought together, the grooves form a channel 22. First and second conductive plates 24 and 26 are positioned between the waveguide portions. Conductive plate 24 includes a connection point 28 for connection to a variable DC voltage source 30 by way of conductor 32. A finline structure 34 is positioned between the conductive plates, which in the preferred embodiment are made of copper.
Insulating sheets 36 and 38 are positioned on opposite sides of conductive plate 24 to insulate it from the conductive waveguide portions. In the preferred embodiment, the insulating sheets are made of mica. Conductive plate 26 is allowed to male electrical contact with the waveguide portions and is connected to an electrical ground either directly, or through the waveguide portions.
FIG. 2 is a side elevation view of a fmline structure 34 that may be used in the phase shifter of FIG. 1, and FIG. 3 is a cross-sectional view of the finline structure 34 talen along line 3-3. Finline structure 34 includes a low dielectric constant, low loss substrate 40 with a layer of tunable material 42 deposited thereon. The preferred embodiment of this invention utilizes Mg0 as the substrate material. The tunable material is metalized with conductive material to form electrodes 46 and 48 that define a gap 44, which separates the electrodes 46 and 48 on the tunable material layer. The gap extends longitudinally from a first end 50 to a second end 52 of the structure. The gap includes a central portion 54 and first and second exponentially tapered end portions 56 and 58 respectively. The end portions are tapered such that the gap widens near the ends to provide impedance matching. Referring to FIG. 1, conductive plates 24 and 26 form exponentially tapered gaps 60 and 62 to provide additional impedance matching. Gaps 60 and 62 lie adjacent to the ends of gap portions 56 and 58 respectively. A plurality of openings, for example 64, 66 and 68, are located in the various components of the phase shifter of FIG. 1 for receiving fasteners that will be used to hold the phase shifter together.
The finline structure is constructed in a unilateral configuration, and in this example, no circuit or metalization is on the rear surface of the substrate 40. The tunable dielectric film on the front of the finline structure is metalized to form two electrodes 46 and 48. In the preferred embodiment, the tunable dielectric film can be a thin film ranging from 0.2 to 2.0 ,um in thickness, or a thick film ranging from 2 to 30 ,um in thickness, with a dielectric constant ranging from 30 to 2000. The exponentially tapered gaps in the metalization on the tunable dielectric material match the impedance at the ends to that of the center tunable region. The center tunable region includes a gap 54 between two generally parallel edges of the metalized conductors with the width of the gap ranging from about 2 to about 50 ,um to form a capacitor. At each end of the tuning region, the same matching structure is mirrored to convert the impedance to that of the free space waveguide.
FIG. 4 is a cross-sectional view of an assembled version of the finline of FIG. 1 taken along line 4-4. In this view, the transverse orientation of the fmline structure within the channel 22 can be seen. In addition, this view shows that conductive plate 26 is electrically connected to the waveguide portions 14 and 16.
DC biasing via the metalized conductors controls the phase shifting. The top conductive plate is isolated using insulating films to prevent voltage breakdown. The bottom part of the finline structure is connected to the waveguide wall or ground.
FIG. 5 is graph of the phase shift versus bias voltage for a phase shifter constructed in accordance with the invention. Curve 72 represents data obtained at 300° K.
FIG. 6 is graph of the losses versus bias voltage for a phase shifter constructed in accordance with the invention. Curve 74 represents the calculated loss tangent. Curve 74 represents the calculated conductor loss. Curve 76 represents the measured device total loss.
The finline mode will propagate through the parallel gap portion of the finline structure. Due to the tunable film dielectric constant decreasing under the biasing voltage, the guided signal will change its phase velocity when passing through this region.
For a 360° phase shift, the total length, L, needed is:
where T is the tunability, and 7~g is the wavelength of a signal guided through the device.
Another method for estimating tunability is using the capacitance variance ratio, such as the ratio, K, of C1, the tuning section capacitance before biasing, to C2, the capacitance after biasing. That is: K = C1/C2. Since the physical dimensions are not changing, this ratio represents the change of effective dielectric constant K
= Eel/~e2, and K =
1/(1-T), where Eel represents the dielectric constant at zero bias voltage and Ee2 represents the dielectric constant at a predetermined bias voltage. For example, a finline phase shifter can have a K of about two, or a tunability of about 50%.
The biasing voltage required to generate a 360° phase shift is about a few hundred volts. FIG. 5 shows the phase response versus biasing voltage, which is approximately a linear relationship. FIG. 6 shows the test results of the phase shifter, indicating that insertion loss is better under the biasing voltage. That is because both the dielectric constant and the loss tangent are decreased under biasing voltage.
A way to estimate the performance of the device is using the figure of merit, which is defined as:
F=
Szi(Ov) ~ Szi(400v) (degree/dB) where 0~ is the total phase change under biasing voltage and Szl is the loss in dB.
This invention provides electronic phase shifters that operate at room temperature and include voltage tunable materials. When a DC tuning voltage is applied to the tunable material, the dielectric constant of the material changes, which causes a change in the group velocity and therefore produces a controllable phase shift.
FIG. 7 is an exploded isometric view of another tunable phase shifter 80 constructed in accordance with an alternative embodiment of the invention. The phase shifter 80 includes a waveguide 82 including side portions 84 and 86. Side portion 84 includes a longitudinal groove 88 and side portion 86 includes a longitudinal groove 90.
When the side portions are brought together, the grooves form a channel 92. A
fmline structure 94 is positioned between the side portions of the waveguide.
FIG. 8 is a side elevation view of a finline structure 94 that may be used in the phase shifter of FIG. 7, and FIG. 9 is a cross-sectional view of the finline structure 94 tal~en along line 9-9. Finline structure 94 includes a low dielectric constant, low loss substrate 96 with a layer of tunable material 98 deposited thereon. The preferred embodiment of this invention utilizes Mg0 as the substrate material. The tunable material is metalized with conductive material to form electrodes 100 and 102 that define a gap 104, which separates the electrodes 100 and 102 on the tunable material layer. The gap extends longitudinally from a first end 106 to a second end 108 of the structure. The gap includes a central portion 110 and first and second exponentially tapered end portions 112 and 114 respectively. The end portions are tapered such that the gap widens near the ends to provide impedance matching. Electrode 102 has a relatively large surface area so that it provides an RF ground to the waveguide structure. In addition, in the embodiment shown in FIG. 8, electrode 102 includes and RF choke design 116 to ensure the RF ground and DC
isolation.
The embodiment shown in FIGs. 7, 8 and 9 uses a spring loaded contact 118 to connect the bias voltage from voltage source 120 to one of the metalized layers on the tunable material. This design reduces the size and simplifies the structure.
Furthermore, the first electrode 100 is DC grounded, while the second electrode 102 is DC
biased and forms an RF ground. The RF ground can be provided via the large area of electrode, or through an RF choke design as shown in FIG. 8, on the substrate to ensure an RF ground.
FIG. 10 is an exploded isometric view of another tunable phase shifter 122 constructed in accordance with another alternative embodiment of the invention. The phase shifter 122 includes a waveguide 124 including side portions 126 and 128. Side portion 126 includes a longitudinal groove 130 and side portion 128 includes a longitudinal groove 1320. When the side portions are brought together, the grooves form a channel 134. A
finline structure 136 is positioned between the side portions of the waveguide.
FIG. 11 is a side elevation view of a finline structure 136 that may be used in the phase shifter of FIG. 10, and FIG. 12 is a cross-sectional view of the finline structure 136 taken along line 12-12. Finline structure 136 includes a low dielectric constant, low loss substrate 138 with a layer of tunable material 140 deposited thereon. The preferred embodiment of this invention utilizes Mg0 as the substrate material. The tunable material is metalized with conductive material to form electrodes 142 and 144 that define a gap 146, which separates the electrodes 142 and 144 on the tunable material layer. The gap extends longitudinally from a first end 148 to a second end 150 of the structure. The gap includes a central portion 152 and first and second exponentially tapered end portions 154 and 156 respectively. The end portions are tapered such that the gap widens near the ends to provide impedance matching.
The embodiment shown in FIGS. 10, 11 and 12 uses a spring loaded contact 158 to connect the bias voltage from voltage source 160 to one of the metallized layers on the tunable material. This design reduces the size and simplifies the structure. Furthermore, the first electrode is DC grounded, while the second electrode is DC biased with an RF
_g_ ground. The RF ground can be provided via the large area of the electrode, or by an RF
choke design on the substrate to ensure RF ground and DC isolation.
Referring to FIG. 10, channel forms tapered sections 162 and 164 to provide additional impedance matching. The tapered section lies adjacent to the ends of gap portions 154 and 156. The embodiment shown in FIGS. 10, 11 and 12 uses a non-standard waveguide to optimize the phase shifter. The non-standard waveguide would then be coupled to a standard waveguide.
In the preferred embodiment the ttmable dielectric layer is preferably comprised of Barium-Strontium Titanate, BaXSrI_XTi03 (BSTO), where x can range from zero to one, or BSTO-composite ceramics. Examples of such BSTO composites include, but are not limited to: BSTO-MgO, BSTO-MgAlz04, BSTO-CaTi03, BSTO-MgTi03, BSTO-MgSrZrTi06, and combinations thereof. Other tunable dielectric materials may be used partially or entirely in place of barium strontium titanate. An example is BaXCaI_ XTi03, where x ranges from 0.2 to 0.8, and preferably from 0.4 to 0.6.
Additional alternative tunable ferroelectrics include PbXZrI_XTi03 (PZT) where x ranges from 0.05 to 0.4, lead lanthanum zirconium titanate (PLZT), lead titanate (PbTiO3), barium calcium zirconium titanate (BaCaZrTi03), sodium nitrate (NaN03), KNb03, LiNb03, LiTaO3, PbNb20~, PbTa206, KSr(Nb03), and NaBa2(Nb03)5 and KHZP04. In addition, the present invention can include electronically tunable materials having at least one metal silicate phase. The metal silicates may.include metals from Group 2A of the Periodic Table, i.e., Be, Mg, Ca, Sr, Ba and Ra, preferably Mg, Ca, Sr and Ba. Preferred metal silicates include Mg2Si04, CaSi03, BaSi03 and SrSi03. In addition to Group 2A metals, the present metal silicates may include metals from Group 1A, i.e., Li, Na, K, Rb, Cs and Fr, preferably Li, Na and K. For example, such metal silicates may include sodium silicates such as Na2Si03 and NaSi03-SH20, and lithium-containing silicates such as LiA1Si04, Li2Si03 and Li4Si04.
Metals from Groups 3A, 4A and some transition metals of the Periodic Table may also be suitable constituents of the metal silicate phase. Additional metal silicates may include AlaSi207, ZrSlO4, KA1S13O8, NaA1S13O8, CaA12Si208, CaMgSI2O~, BaT1S13O9 and ZnZSIO4.
The above tunable materials can be tuned at room temperature by controlling an electric field that is applied across the materials.
This invention utilizes a fmline structure that is disposed within a waveguide.
The structure includes a low loss substrate and a tunable dielectric film. The tunable film is metalized to form two conductors. Impedance matching is provided by using exponentially tapered sections of a gap between the conductors. In one embodiment, at the leading edge of the waveguide, two copper plate sections match free-space waveguide to the dielectric substrate, which is sandwiched between the copper plates. On the dielectric substrate, tapered metalized sections on the tunable film match the impedance to the center tunable region.
Tlus invention takes advantage of a high dielectric constant of voltage tunable thick film materials, such as BSTO, to build a 360° waveguide-finline phase shifter.
The phase shifters of this invention can be electronically tuned to provide repeatable and stable phase shifts. Since the tunable material is a good insulator, the DC
power consumption of the tuning voltage supply is very low, with a current typically less than a microampere. The voltage tuned phase shifters have the advantage of fast tuning, good tunability, small size, simple control circuits, low power consumption, and low cost.
In addition, the phase shifters show good linear behavior and can be radiation hardened.
An example of an application of the phase shifters of this invention is in phased array antennas. An array of radiating elements generates a specified beam pattern, with each element controlled by a phase shifter and the array of elements working together to form a beam in a desired direction. A 360° phase shifter can direct the radiating electromagnetic energy to any specified direction without mechanically moving the radiating element. By assembling a number of antenna elements to form a phased array, the direction of the main lobe of the beam, can be controlled. This is achieved through the adjustment of the signal amplitude and phase of each antenna element in the array. The advantage of phase array antennas is their accurate pointing of the beam in the specified direction that minimizes radiation in unwanted directions, and improves the signal-to-noise ratio and overall efficiency of the system.
In phased array antenna applications, the phase control needs to be accurate, reliable and fast. By using the present tunable phase shifter in phased array antennas, an accurate phase shift will be easier to obtain by tuning a DC voltage. The phase shift versus tuning voltage is an approximately linear relationship. In addition, higher power applications can be realized by using waveguide structure phase shifters.
While the present invention has been described in terms of what are at present believed to be its preferred embodiments, it will be apparent to those skilled in the art that various changes may be made to the disclosed embodiments without departing from the scope of the invention as defined by the following claims.
FIG. 4 is a cross-sectional view of an assembled version of the finline of FIG. 1 taken along line 4-4. In this view, the transverse orientation of the fmline structure within the channel 22 can be seen. In addition, this view shows that conductive plate 26 is electrically connected to the waveguide portions 14 and 16.
DC biasing via the metalized conductors controls the phase shifting. The top conductive plate is isolated using insulating films to prevent voltage breakdown. The bottom part of the finline structure is connected to the waveguide wall or ground.
FIG. 5 is graph of the phase shift versus bias voltage for a phase shifter constructed in accordance with the invention. Curve 72 represents data obtained at 300° K.
FIG. 6 is graph of the losses versus bias voltage for a phase shifter constructed in accordance with the invention. Curve 74 represents the calculated loss tangent. Curve 74 represents the calculated conductor loss. Curve 76 represents the measured device total loss.
The finline mode will propagate through the parallel gap portion of the finline structure. Due to the tunable film dielectric constant decreasing under the biasing voltage, the guided signal will change its phase velocity when passing through this region.
For a 360° phase shift, the total length, L, needed is:
where T is the tunability, and 7~g is the wavelength of a signal guided through the device.
Another method for estimating tunability is using the capacitance variance ratio, such as the ratio, K, of C1, the tuning section capacitance before biasing, to C2, the capacitance after biasing. That is: K = C1/C2. Since the physical dimensions are not changing, this ratio represents the change of effective dielectric constant K
= Eel/~e2, and K =
1/(1-T), where Eel represents the dielectric constant at zero bias voltage and Ee2 represents the dielectric constant at a predetermined bias voltage. For example, a finline phase shifter can have a K of about two, or a tunability of about 50%.
The biasing voltage required to generate a 360° phase shift is about a few hundred volts. FIG. 5 shows the phase response versus biasing voltage, which is approximately a linear relationship. FIG. 6 shows the test results of the phase shifter, indicating that insertion loss is better under the biasing voltage. That is because both the dielectric constant and the loss tangent are decreased under biasing voltage.
A way to estimate the performance of the device is using the figure of merit, which is defined as:
F=
Szi(Ov) ~ Szi(400v) (degree/dB) where 0~ is the total phase change under biasing voltage and Szl is the loss in dB.
This invention provides electronic phase shifters that operate at room temperature and include voltage tunable materials. When a DC tuning voltage is applied to the tunable material, the dielectric constant of the material changes, which causes a change in the group velocity and therefore produces a controllable phase shift.
FIG. 7 is an exploded isometric view of another tunable phase shifter 80 constructed in accordance with an alternative embodiment of the invention. The phase shifter 80 includes a waveguide 82 including side portions 84 and 86. Side portion 84 includes a longitudinal groove 88 and side portion 86 includes a longitudinal groove 90.
When the side portions are brought together, the grooves form a channel 92. A
fmline structure 94 is positioned between the side portions of the waveguide.
FIG. 8 is a side elevation view of a finline structure 94 that may be used in the phase shifter of FIG. 7, and FIG. 9 is a cross-sectional view of the finline structure 94 tal~en along line 9-9. Finline structure 94 includes a low dielectric constant, low loss substrate 96 with a layer of tunable material 98 deposited thereon. The preferred embodiment of this invention utilizes Mg0 as the substrate material. The tunable material is metalized with conductive material to form electrodes 100 and 102 that define a gap 104, which separates the electrodes 100 and 102 on the tunable material layer. The gap extends longitudinally from a first end 106 to a second end 108 of the structure. The gap includes a central portion 110 and first and second exponentially tapered end portions 112 and 114 respectively. The end portions are tapered such that the gap widens near the ends to provide impedance matching. Electrode 102 has a relatively large surface area so that it provides an RF ground to the waveguide structure. In addition, in the embodiment shown in FIG. 8, electrode 102 includes and RF choke design 116 to ensure the RF ground and DC
isolation.
The embodiment shown in FIGs. 7, 8 and 9 uses a spring loaded contact 118 to connect the bias voltage from voltage source 120 to one of the metalized layers on the tunable material. This design reduces the size and simplifies the structure.
Furthermore, the first electrode 100 is DC grounded, while the second electrode 102 is DC
biased and forms an RF ground. The RF ground can be provided via the large area of electrode, or through an RF choke design as shown in FIG. 8, on the substrate to ensure an RF ground.
FIG. 10 is an exploded isometric view of another tunable phase shifter 122 constructed in accordance with another alternative embodiment of the invention. The phase shifter 122 includes a waveguide 124 including side portions 126 and 128. Side portion 126 includes a longitudinal groove 130 and side portion 128 includes a longitudinal groove 1320. When the side portions are brought together, the grooves form a channel 134. A
finline structure 136 is positioned between the side portions of the waveguide.
FIG. 11 is a side elevation view of a finline structure 136 that may be used in the phase shifter of FIG. 10, and FIG. 12 is a cross-sectional view of the finline structure 136 taken along line 12-12. Finline structure 136 includes a low dielectric constant, low loss substrate 138 with a layer of tunable material 140 deposited thereon. The preferred embodiment of this invention utilizes Mg0 as the substrate material. The tunable material is metalized with conductive material to form electrodes 142 and 144 that define a gap 146, which separates the electrodes 142 and 144 on the tunable material layer. The gap extends longitudinally from a first end 148 to a second end 150 of the structure. The gap includes a central portion 152 and first and second exponentially tapered end portions 154 and 156 respectively. The end portions are tapered such that the gap widens near the ends to provide impedance matching.
The embodiment shown in FIGS. 10, 11 and 12 uses a spring loaded contact 158 to connect the bias voltage from voltage source 160 to one of the metallized layers on the tunable material. This design reduces the size and simplifies the structure. Furthermore, the first electrode is DC grounded, while the second electrode is DC biased with an RF
_g_ ground. The RF ground can be provided via the large area of the electrode, or by an RF
choke design on the substrate to ensure RF ground and DC isolation.
Referring to FIG. 10, channel forms tapered sections 162 and 164 to provide additional impedance matching. The tapered section lies adjacent to the ends of gap portions 154 and 156. The embodiment shown in FIGS. 10, 11 and 12 uses a non-standard waveguide to optimize the phase shifter. The non-standard waveguide would then be coupled to a standard waveguide.
In the preferred embodiment the ttmable dielectric layer is preferably comprised of Barium-Strontium Titanate, BaXSrI_XTi03 (BSTO), where x can range from zero to one, or BSTO-composite ceramics. Examples of such BSTO composites include, but are not limited to: BSTO-MgO, BSTO-MgAlz04, BSTO-CaTi03, BSTO-MgTi03, BSTO-MgSrZrTi06, and combinations thereof. Other tunable dielectric materials may be used partially or entirely in place of barium strontium titanate. An example is BaXCaI_ XTi03, where x ranges from 0.2 to 0.8, and preferably from 0.4 to 0.6.
Additional alternative tunable ferroelectrics include PbXZrI_XTi03 (PZT) where x ranges from 0.05 to 0.4, lead lanthanum zirconium titanate (PLZT), lead titanate (PbTiO3), barium calcium zirconium titanate (BaCaZrTi03), sodium nitrate (NaN03), KNb03, LiNb03, LiTaO3, PbNb20~, PbTa206, KSr(Nb03), and NaBa2(Nb03)5 and KHZP04. In addition, the present invention can include electronically tunable materials having at least one metal silicate phase. The metal silicates may.include metals from Group 2A of the Periodic Table, i.e., Be, Mg, Ca, Sr, Ba and Ra, preferably Mg, Ca, Sr and Ba. Preferred metal silicates include Mg2Si04, CaSi03, BaSi03 and SrSi03. In addition to Group 2A metals, the present metal silicates may include metals from Group 1A, i.e., Li, Na, K, Rb, Cs and Fr, preferably Li, Na and K. For example, such metal silicates may include sodium silicates such as Na2Si03 and NaSi03-SH20, and lithium-containing silicates such as LiA1Si04, Li2Si03 and Li4Si04.
Metals from Groups 3A, 4A and some transition metals of the Periodic Table may also be suitable constituents of the metal silicate phase. Additional metal silicates may include AlaSi207, ZrSlO4, KA1S13O8, NaA1S13O8, CaA12Si208, CaMgSI2O~, BaT1S13O9 and ZnZSIO4.
The above tunable materials can be tuned at room temperature by controlling an electric field that is applied across the materials.
This invention utilizes a fmline structure that is disposed within a waveguide.
The structure includes a low loss substrate and a tunable dielectric film. The tunable film is metalized to form two conductors. Impedance matching is provided by using exponentially tapered sections of a gap between the conductors. In one embodiment, at the leading edge of the waveguide, two copper plate sections match free-space waveguide to the dielectric substrate, which is sandwiched between the copper plates. On the dielectric substrate, tapered metalized sections on the tunable film match the impedance to the center tunable region.
Tlus invention takes advantage of a high dielectric constant of voltage tunable thick film materials, such as BSTO, to build a 360° waveguide-finline phase shifter.
The phase shifters of this invention can be electronically tuned to provide repeatable and stable phase shifts. Since the tunable material is a good insulator, the DC
power consumption of the tuning voltage supply is very low, with a current typically less than a microampere. The voltage tuned phase shifters have the advantage of fast tuning, good tunability, small size, simple control circuits, low power consumption, and low cost.
In addition, the phase shifters show good linear behavior and can be radiation hardened.
An example of an application of the phase shifters of this invention is in phased array antennas. An array of radiating elements generates a specified beam pattern, with each element controlled by a phase shifter and the array of elements working together to form a beam in a desired direction. A 360° phase shifter can direct the radiating electromagnetic energy to any specified direction without mechanically moving the radiating element. By assembling a number of antenna elements to form a phased array, the direction of the main lobe of the beam, can be controlled. This is achieved through the adjustment of the signal amplitude and phase of each antenna element in the array. The advantage of phase array antennas is their accurate pointing of the beam in the specified direction that minimizes radiation in unwanted directions, and improves the signal-to-noise ratio and overall efficiency of the system.
In phased array antenna applications, the phase control needs to be accurate, reliable and fast. By using the present tunable phase shifter in phased array antennas, an accurate phase shift will be easier to obtain by tuning a DC voltage. The phase shift versus tuning voltage is an approximately linear relationship. In addition, higher power applications can be realized by using waveguide structure phase shifters.
While the present invention has been described in terms of what are at present believed to be its preferred embodiments, it will be apparent to those skilled in the art that various changes may be made to the disclosed embodiments without departing from the scope of the invention as defined by the following claims.
Claims (20)
1. A tunable phase shifter comprising;
a waveguide;
a finline substrate positioned within the waveguide;
a tunable dielectric Layer positioned on the finline substrate;
a first conductor positioned on the tunable dielectric layer; and a second conductor positioned on the tunable dielectric layer, the first and second conductors being separated to form a gap;
wherein the first conductor is insulated from the waveguide, and the second conductor is electrically connected to the waveguide.
a waveguide;
a finline substrate positioned within the waveguide;
a tunable dielectric Layer positioned on the finline substrate;
a first conductor positioned on the tunable dielectric layer; and a second conductor positioned on the tunable dielectric layer, the first and second conductors being separated to form a gap;
wherein the first conductor is insulated from the waveguide, and the second conductor is electrically connected to the waveguide.
2. A tunable phase shifter according to claim 1, wherein:
the gap extends from a first end of the tunable dielectric layer to a second end of the tunable dielectric layer;
the gap includes a first end, a center portion and a second end; and the gap includes exponentially tapered portions adjacent to said first and second ends.
the gap extends from a first end of the tunable dielectric layer to a second end of the tunable dielectric layer;
the gap includes a first end, a center portion and a second end; and the gap includes exponentially tapered portions adjacent to said first and second ends.
3. A tunable phase shifter according to claim 2, wherein the gap has a minimum width ranging from 2 micron to 50 micron.
4. A tunable phase shifter according to claim 1, further comprising:
a voltage source for applying a control voltage between the first conductor and the second conductor.
a voltage source for applying a control voltage between the first conductor and the second conductor.
5. A tunable phase shifter according to claim 1, wherein the second conductor forms an RF ground.
6. A tunable phase shifter according to claim 1, wherein the second conductor comprises:
an RF choke.
an RF choke.
7. A tunable phase shifter according to claim 1, wherein the waveguide includes first and second sections, and the tunable phase shifter further comprises:
a first conductive plate positioned between the first and second sections of the waveguide; and a second conductive plate positioned between the first and second sections of the waveguide, the first conductive plate being insulated from the waveguide and the second conductive plate being electrically connected to the waveguide.
a first conductive plate positioned between the first and second sections of the waveguide; and a second conductive plate positioned between the first and second sections of the waveguide, the first conductive plate being insulated from the waveguide and the second conductive plate being electrically connected to the waveguide.
8. A tunable phase shifter according to claim 7, further comprising an impedance matching section formed by a gap between the first and second conductive plates.
9. A tunable phase shifter according to claim 8, wherein the impedance matching section comprises:
an exponentially tapered gap between the first and second conductive plates.
an exponentially tapered gap between the first and second conductive plates.
10. A tunable phase shifter according to claim 1, wherein the first conductor includes an RF ground.
11. A tunable phase shifter according to claim 10, further comprising an impedance matching section formed by a gap between the first and second conductors.
12. A tunable phase shifter according to claim 11, wherein the impedance matching section comprises:
an exponentially tapered gap between the first and second conductors.
an exponentially tapered gap between the first and second conductors.
13. A tunable phase shifter according to claim 1, wherein the tunable dielectric layer comprises a material selected from the group of:
barium calcium titanate, lead zirconium titanate, lead lanthanum zirconium titanate, lead titanate, barium calcium zirconium titanate, sodium nitrate, KNbO3, LiNbO3, LiTaO3, PbNb2O6, PbTa2O6, KSr(NbO3), NaBa2(NbO3)5, KH2PO4, and combinations thereof.
barium calcium titanate, lead zirconium titanate, lead lanthanum zirconium titanate, lead titanate, barium calcium zirconium titanate, sodium nitrate, KNbO3, LiNbO3, LiTaO3, PbNb2O6, PbTa2O6, KSr(NbO3), NaBa2(NbO3)5, KH2PO4, and combinations thereof.
14. A tunable phase shifter according to claim 1, wherein the tunable dielectric layer comprises a barium strontium titanate (BSTO) composite selected from the group of:
BSTO-MgAl2O4, BSTO-CaTiO3, BSTO-MgTiO3, BSTO-MgSrZrTiO6, and combinations thereof.
BSTO-MgAl2O4, BSTO-CaTiO3, BSTO-MgTiO3, BSTO-MgSrZrTiO6, and combinations thereof.
15. A tunable phase shifter according to claim 1, wherein the tunable dielectric layer comprises a material selected from the group of:
Mg2SiO4, CaSiO3, BaSiO3, SrSiO3, Na2SiO3, NaSiO3-5H2O, LiAlSiO4, Li2SiO3, Li4SiO4, Al2Si2O7, ZrSiO4, KAlSi3O8, NaAlSi3O8, CaAl2Si2O8, CaMgSizO6, BaTiSi3O9 and Zn2SiO4.
Mg2SiO4, CaSiO3, BaSiO3, SrSiO3, Na2SiO3, NaSiO3-5H2O, LiAlSiO4, Li2SiO3, Li4SiO4, Al2Si2O7, ZrSiO4, KAlSi3O8, NaAlSi3O8, CaAl2Si2O8, CaMgSizO6, BaTiSi3O9 and Zn2SiO4.
16. A tunable phase shifter according to claim 1, wherein the tunable dielectric layer comprises:
an electronically tunable dielectric phase and at least two metal oxide phases.
an electronically tunable dielectric phase and at least two metal oxide phases.
17. A tunable phase shifter according to claim 1, wherein the tunable dielectric layer has a dielectric constant at zero bias voltage ranging from 30 to 2000.
18. A tunable phase shifter according to claim 1, wherein the a finline substrate comprises:
a low loss, low dielectric material.
a low loss, low dielectric material.
19. A tunable phase shifter according to claim 1, wherein the tunable dielectric layer comprises barium strontium titanate
20. A tunable phase shifter according to claim 1, wherein the tunable dielectric layer comprises BSTO-MgO.
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| US19869000P | 2000-04-20 | 2000-04-20 | |
| US60/198,690 | 2000-04-20 | ||
| PCT/US2001/012722 WO2001082404A1 (en) | 2000-04-20 | 2001-04-19 | Waveguide-finline tunable phase shifter |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CA2405794A1 true CA2405794A1 (en) | 2001-11-01 |
Family
ID=22734392
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CA002405794A Abandoned CA2405794A1 (en) | 2000-04-20 | 2001-04-19 | Waveguide-finline tunable phase shifter |
Country Status (5)
| Country | Link |
|---|---|
| US (1) | US6985050B2 (en) |
| EP (1) | EP1287579A1 (en) |
| AU (1) | AU2001255481A1 (en) |
| CA (1) | CA2405794A1 (en) |
| WO (1) | WO2001082404A1 (en) |
Families Citing this family (16)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| EP1698018A1 (en) * | 2003-12-24 | 2006-09-06 | Molex Incorporated | Transmission line having a transforming impedance |
| JP2007518311A (en) * | 2003-12-24 | 2007-07-05 | モレックス インコーポレーテッド | Triangular matching transmission structure |
| JP4351282B2 (en) * | 2004-03-09 | 2009-10-28 | テレフオンアクチーボラゲット エル エム エリクソン（パブル） | Improved adjustable delay line |
| WO2008145165A1 (en) * | 2007-05-31 | 2008-12-04 | Telecom Italia S.P.A. | Ferroelectric delay line |
| FR2922064B1 (en) * | 2007-10-05 | 2011-04-15 | Thales Sa | METHOD FOR CONTROLLING INTELLIGENT ANTENNAS WITHIN A COMMUNICATION NETWORK |
| US7805767B2 (en) * | 2008-10-06 | 2010-10-05 | Bae Systems Land & Armaments | Body armor plate having integrated electronics modules |
| US8797126B2 (en) * | 2008-12-01 | 2014-08-05 | Telefonaktiebolaget L M Ericsson (Publ) | Tunable microwave arrangements |
| US8502506B2 (en) * | 2010-01-15 | 2013-08-06 | Bae Systems Aerospace & Defense Group Inc. | Portable electrical power source for incorporation with an armored garment |
| US9147924B2 (en) * | 2011-09-02 | 2015-09-29 | The United States Of America As Represented By The Secretary Of The Army | Waveguide to co-planar-waveguide (CPW) transition |
| JP2015076661A (en) * | 2013-10-07 | 2015-04-20 | 日本電気株式会社 | Coaxial wiring device and transmission/reception integral splitter |
| CN105793955B (en) | 2013-11-06 | 2019-09-13 | 应用材料公司 | Suppressor is generated by the particle of DC bias modulation |
| US10027005B2 (en) | 2016-01-29 | 2018-07-17 | Northrop Grumman Systems Corporation | Voltage controlled tunable filter |
| WO2018120196A1 (en) * | 2016-12-30 | 2018-07-05 | 华为技术有限公司 | Phase shifter, phase shift array and communication device |
| US10892549B1 (en) | 2020-02-28 | 2021-01-12 | Northrop Grumman Systems Corporation | Phased-array antenna system |
| CN111533554B (en) * | 2020-04-30 | 2022-03-11 | 福建火炬电子科技股份有限公司 | High-voltage ceramic pulse capacitor, dielectric material and preparation method thereof |
| CN114374066B (en) * | 2022-01-18 | 2023-06-02 | 西南应用磁学研究所(中国电子科技集团公司第九研究所) | Ultra-wideband high-power circulator for star |
Family Cites Families (27)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| FR2412960A1 (en) | 1977-12-20 | 1979-07-20 | Radant Etudes | HYPERFREQUENCY DEPHASER AND ITS APPLICATION TO ELECTRONIC SCAN |
| US4291415A (en) * | 1979-12-03 | 1981-09-22 | Microwave Associates, Inc. | Microwave integrated circuit double balanced mixer |
| GB2086143A (en) * | 1980-10-22 | 1982-05-06 | Philips Electronic Associated | Finline circuit configuration |
| US4434409A (en) | 1981-06-11 | 1984-02-28 | Raytheon Company | Dielectric waveguide phase shifter |
| US4532704A (en) | 1981-06-11 | 1985-08-06 | Raytheon Company | Dielectric waveguide phase shifter |
| EP0185446A3 (en) * | 1984-10-12 | 1988-03-30 | British Aerospace Public Limited Company | Transmitter/receiver |
| US4568893A (en) * | 1985-01-31 | 1986-02-04 | Rca Corporation | Millimeter wave fin-line reflection phase shifter |
| US4728904A (en) * | 1985-05-24 | 1988-03-01 | Trw Inc. | Extra high frequency (EHF) circuit module |
| US4818963A (en) | 1985-06-05 | 1989-04-04 | Raytheon Company | Dielectric waveguide phase shifter |
| US4654611A (en) | 1985-10-02 | 1987-03-31 | Hughes Aircraft Company | Broadband waveguide phase shifter |
| US4782346A (en) | 1986-03-11 | 1988-11-01 | General Electric Company | Finline antennas |
| US4789840A (en) | 1986-04-16 | 1988-12-06 | Hewlett-Packard Company | Integrated capacitance structures in microwave finline devices |
| DE3782332D1 (en) | 1987-02-21 | 1992-11-26 | Ant Nachrichtentech | PHASE SHIFT. |
| IT1223796B (en) | 1988-09-02 | 1990-09-29 | Cselt Centro Studi Lab Telecom | COAXIAL WAVER GUIDE CHANGER |
| US4894627A (en) | 1989-01-03 | 1990-01-16 | Motorola, Inc. | Directional waveguide-finline coupler |
| JPH05251942A (en) * | 1992-03-05 | 1993-09-28 | Mitsubishi Electric Corp | Frequency converter |
| US5355104A (en) | 1993-01-29 | 1994-10-11 | Hughes Aircraft Company | Phase shift device using voltage-controllable dielectrics |
| US5312790A (en) | 1993-06-09 | 1994-05-17 | The United States Of America As Represented By The Secretary Of The Army | Ceramic ferroelectric material |
| US5693429A (en) | 1995-01-20 | 1997-12-02 | The United States Of America As Represented By The Secretary Of The Army | Electronically graded multilayer ferroelectric composites |
| US5811830A (en) | 1995-06-08 | 1998-09-22 | The United States Of America As Represented By The Secretary Of The Army | Quantum well optical waveguide phase shifter |
| US5635434A (en) | 1995-09-11 | 1997-06-03 | The United States Of America As Represented By The Secretary Of The Army | Ceramic ferroelectric composite material-BSTO-magnesium based compound |
| US5635433A (en) | 1995-09-11 | 1997-06-03 | The United States Of America As Represented By The Secretary Of The Army | Ceramic ferroelectric composite material-BSTO-ZnO |
| US5766697A (en) | 1995-12-08 | 1998-06-16 | The United States Of America As Represented By The Secretary Of The Army | Method of making ferrolectric thin film composites |
| US5846893A (en) | 1995-12-08 | 1998-12-08 | Sengupta; Somnath | Thin film ferroelectric composites and method of making |
| US5830591A (en) | 1996-04-29 | 1998-11-03 | Sengupta; Louise | Multilayered ferroelectric composite waveguides |
| US5724011A (en) | 1996-09-03 | 1998-03-03 | Hughes Electronics | Voltage variable dielectric ridged waveguide phase shifter |
| US6096127A (en) * | 1997-02-28 | 2000-08-01 | Superconducting Core Technologies, Inc. | Tuneable dielectric films having low electrical losses |
-
2001
- 2001-04-19 US US09/838,483 patent/US6985050B2/en not_active Expired - Lifetime
- 2001-04-19 CA CA002405794A patent/CA2405794A1/en not_active Abandoned
- 2001-04-19 WO PCT/US2001/012722 patent/WO2001082404A1/en not_active Application Discontinuation
- 2001-04-19 AU AU2001255481A patent/AU2001255481A1/en not_active Abandoned
- 2001-04-19 EP EP01928647A patent/EP1287579A1/en not_active Withdrawn
Also Published As
| Publication number | Publication date |
|---|---|
| AU2001255481A1 (en) | 2001-11-07 |
| WO2001082404A1 (en) | 2001-11-01 |
| EP1287579A1 (en) | 2003-03-05 |
| US20020033744A1 (en) | 2002-03-21 |
| US6985050B2 (en) | 2006-01-10 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| US6954118B2 (en) | Voltage tunable coplanar phase shifters with a conductive dome structure | |
| US6377217B1 (en) | Serially-fed phased array antennas with dielectric phase shifters | |
| EP1121725B1 (en) | Voltage tunable varactors and tunable devices including such varactors | |
| EP1281210B1 (en) | Microstrip phase shifter | |
| US6556102B1 (en) | RF/microwave tunable delay line | |
| US5504466A (en) | Suspended dielectric and microstrip type microwave phase shifter and application to lobe scanning antenne networks | |
| US6985050B2 (en) | Waveguide-finline tunable phase shifter | |
| KR20010089305A (en) | Voltage tunable laminated dielectric materials for microwave applications | |
| WO2001033660A1 (en) | Microstrip tunable filters tuned by dielectric varactors | |
| US8279129B1 (en) | Transverse device phase shifter | |
| EP1530249B1 (en) | Voltage tunable coplanar phase shifters | |
| Rao et al. | A Novel phased array antenna that uses ferroelectrics and bulk phase shifting |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| FZDE | Dead |