CA2032058C - Circuit for dimming gas discharge lamps without introducing striations - Google Patents
Circuit for dimming gas discharge lamps without introducing striations Download PDFInfo
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- CA2032058C CA2032058C CA002032058A CA2032058A CA2032058C CA 2032058 C CA2032058 C CA 2032058C CA 002032058 A CA002032058 A CA 002032058A CA 2032058 A CA2032058 A CA 2032058A CA 2032058 C CA2032058 C CA 2032058C
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- current
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- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
- H05B41/14—Circuit arrangements
- H05B41/36—Controlling
- H05B41/38—Controlling the intensity of light
- H05B41/39—Controlling the intensity of light continuously
- H05B41/392—Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor
- H05B41/3921—Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor with possibility of light intensity variations
- H05B41/3927—Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor with possibility of light intensity variations by pulse width modulation
-
- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
- H05B41/14—Circuit arrangements
- H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
- H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
- H05B41/282—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices
- H05B41/285—Arrangements for protecting lamps or circuits against abnormal operating conditions
- H05B41/2858—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the lamp against abnormal operating conditions
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B20/00—Energy efficient lighting technologies, e.g. halogen lamps or gas discharge lamps
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
- Y10S—TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y10S315/00—Electric lamp and discharge devices: systems
- Y10S315/04—Dimming circuit for fluorescent lamps
Abstract
A control system for providing electrical power from a source to a gas discharge lamp. The system com-prises a circuit for providing symmetrical ac current to the electrodes of the lamp to strike and maintain an electric discharge through the lamp, and a circuit for simultaneously providing dc current to the lamp electrodes.
An asymmetric current waveform is established in the lamp which substantially eliminates the occurrence of visible striations.
An asymmetric current waveform is established in the lamp which substantially eliminates the occurrence of visible striations.
Description
~03205~
CIRCUIT FOR DIMMING GAS DISCHARGE
LAMPS WITHOUT INTRODUCING STRIATIONS
Background of the Invention Field of the Invention This invention pertains to dimming gas discharge lamps and, more particularly, to dimming compact fluores-cent lamps.
Description of the Related Axt A gas discharge lamp converts electrical energy into visible energy with high efficiency. A gas discharge lamp is generally an elongated gas-filled (usually low pressure mercury vapor) tube having electrodes at each end.
Each electrode is formed from a resistive filament (usually tungsten) coated with a thermionically emissive material, such as a mixture of alkaline earth oxides.
The steady-state operation of a gas discharge lamp is as follows: Voltage is applied across the resistive filaments, heating the electrodes to a temperature suffi-cient to cause thermionic emission of electrons into the discharge tube. A voltage applied between the electrodes accelerates the electrons toward the anode. En route to the anode, the electrons collide with gas atoms to produce positive ions and additional electrons, forming in the tube a gas plasma of positive and negative charge carriers. The electrons continue to stream toward the anode and the 6232-107.CN -1-/lp/#11 positive ions toward the cathode, sustaining an electric discharge in the tube and further heating the electrodes.
(If the applied power is ac, the electrodes reverse polar-ity during each half cycle.) The discharge causes the emission of radiation having a wavelength dependent upon the particular fill gas and the electrical parameters of the discharge. Because each collision produces additional electrons and ions, increases in the arc current can cause the impedance of the lamp to decrease, a characteristic known as "negative resistance." Operation of the lamp is inherently unstable, due to this negative resistance characteristic, and current between the electrodes must be limited by external means to avoid damaging the lamp.
Dimming of gas discharge lamps is well known. A
circuit for dimming conventional fluorescent gas discharge lamp is disclosed in U.S. Patent No. 3,927,345, issued December 16, 1975, to Licata et al. A fluorescent lamp is a gas discharge lamp in which the inner surface of the tube is coated with a fluorescent phosphor. The phosphor is excited by ultraviolet radiation from the electric discharge and fluoresces, providing visible light. Licata discloses a phase control dimming circuit which provides phase controlled voltage from a 60Iiz ac source to a fluorescent lamp in series with an inductive ballast. The dimxcir~g . circuit employs a bidirectional triode-type thyristor (triac) as the main switching device and includes a ~c compensation circuit to ensure symmetrical triac firing delays in each half cycle of power flow from the ac source: There is no current through the lamp during the triac firing delay. Symmetrically firing the triac prevents excessive amount of do current from flowing through the lamp, which can cause lamp flickering and saturation of the inductive ballast. The circuit operates over a dimming range from about 100% to 50~ of full light output. Below about 500 light output, 6232-107.CN -2-/ 1 p/'~ 11 ~o~~~~~
the electrical discharge cannot be sustained, because the triac firing delay is longer than the recombination time of the gas plasma in the discharge tube.
U.S. Patent No. 4,001,637 issued January 4, 1977, to Gray, discloses a gas discharge Iamp dimming circuit that is capable of operating lamps at dimming levels below 50% of full light output. how dimming levels are attained by providing uninterrupted filtered do current to the lamp.
The circuit includes a capacitative ballast, a full wave rectifier, and an output filter. Ac current flows from a phase controlled source through the capacitive ballast to a full-wave rectifier. Pulsating do current is provided by the full-wave rectifier to an LC low pass filter and then to the lamp electrodes. However, do current tends to cause anode oscillations, uneven illumination along the length of the lamp, and a reduction in useful lamp life.
Anodes oscillations can be greatly reduced by operating a lamp at frequencies much higher than the fundamental frequency of the anode oscillation. U.S.
Patent No. 4,207,498, issued June 10, 1980, to Spires et al., discloses a dimming system that includes a central inverter for providing a 23kHz ac current through the lamp.
The lamp can be dimmed over a range form 100% to 1% of full light output by adjusting the amplitude of the inverter output. The use of high-frequency ac current also may increase the efficacy of the lamp by as much as 20%.
At low light levels (less than about 30% of full light output), however, the lamp tends to '°striate"; i.e., to break up into alternating bands of bright and dim areas along the length of the tube. The mechanisms that cause striation are not completely understood, but it is believed to result from high-frequency currents reinforcing a standing wave of varying charge distribution between the lamp electrodes. For reasons that are not clear, small-diameter lamps and lamps with sharp bends (typical charac-6232-107.CN -3-/lp/#11 zo3;Do~s teristics of compact fluorescent lamps) are more likely to striate.
Summary of the Invention The present invention provides a dimming control circuit for compact fluorescent lamps which greatly reduces striation while maintaining a flicker-free dimming range from about 1000 to 1~ of full light output. The dimming circuit generally provides 27kHz sinusoidal current to the lamp electrodes to initiate and maintain an electric discharge through the lamp and, simultaneously, provides a small amount of substantially non-pulsating do current to the electrodes to produce an asymmetric current waveform through the lamp. The asymmetric currant flow greatly reduces visible striations in the lamp. We believed that asymmetry alters the charge distribution in the tube to prevent formation of a standing wave between the lamp electrodes. Although a wave-like variation in charge distribution can be measured along the discharge tube, it is not a standing wave; it moves with a velocity that is determined by the magnitude of the do component of current flow through the lamp. Visible striations are eliminated by providing to the lamps a do current that causes the bright and dim bands, produced by the wave-like charge distribution, to move rapidly, so they become impercep-tible. Too much do current, however, causes anode oscil-lations. A suitable amount of do current is selected by compromising between the effects of striations and anode oscillations. It has been .found experimentally that a do current of about .04 to l.4mA satisfactorily achieves this compromise for a typical compact fluorescent lamp. Genera-lly, the optimum do current increases over the dimming range between minimum and mid range power. At higher powers, the precise value of do current is less critical.
The ratio of do current in the low-to-mid range is prefer-ably about 1:2. Thus, preferred do currents axe about 0.04 6232-107.CN -4-/lp/#11 2~32~65~
to 0.7mA and about 0.1 to l.4mA at minimum and half-maximum lamp powers, respectively.
According to the present invention, a control system for providing electrical power from a source to a gas discharge lamp comprises:
a) means fox providing symmetrical ac current to the electrodes of said lamp to strike and maintain an electric discharge therethrough; and b) means for simultaneously providing do current to said lamp electrodes;
whereby an asymmetric current waveform is established in the lamp, substantially eliminating the occurrence of visible striations.
In another embodiment of the present invention, a i5 control system for providing electrical power from a source to a pair of gas discharge lamps connected in series comprises:
a) means for providing symmetrical ac current to the electrodes of said lamps to strike and maintain an electric discharge therethrough; and b) means for simultaneously providing do current to said lamp electrodes;
whereby an asymmetric current waveform is established in the lamps, substantially eliminating the occurrence of visible striations.
Brief Description of the Drawings Fig. 1 is a block diagram of a dimming circuit of the present invention.
Fig. 2 is a graph of current flow through a compact fluorescent lamp according to the present invention.
Fig. 3 is a circuit schematic of a dimming circuit of the present invention.
6232-107.CN -5-/lp/#11 2p3~?05~
Detailed Description of the Present Invention Fig. 1 shows a block diagram of the dimming circuit of the present invention. The dimming circuit 1, enclosed in the dashed lines, provides a variable amount of power from sinusoidal power source 3 to a gas discharge lamp 5.
The dimming circuit generally includes a front-end rec-tifier 7 to convert a (typically) 60Hz ac voltage from power source 3 into a do voltage provided to switching inverter 9. Switching inverter 9 converts the do voltage into a high-frequency ac voltage consisting of alternately inverted and non-inverted rectangular pulses of voltage having variable duration. Pulse duration modulation (PDM) circuit 11 provides a modulating voltage waveform to switching inverter 9 to control the duration of each pulse.
The high-frequency ac voltage from switching inverter 9 drives resonant circuit 13 so that it resonates substantially sinusoidally, with an amplitude determined by the amplitude and frequency of the driving voltage and the magnification factor Q of the resonant circuit. The resonant circuit is essentially a symmetrical high-frequen-cy sinusoidal current source with a variable amplitude determined by the pulse duration of the driving voltage from switching inverter 9. In this specification and the appended claims, a resonant circuit is understood to have a single fundamental mode of resonance. The term "peak response frequency" refers to the frequency at which this fundamental resonance is maximized. As applied to ac waveforms, the term °'symmetrical" is understood to mean that the positive portion of the waveform is substantially identical in shape and magnitude to the corresponding negative portion of the waveform.
The current from resonant circuit 13 is provided to lamp 5 to strike and maintain a stable electric discharge over a range of selectable power levels. Simultaneously, back-end rectifier 15 rectifies a predetermined amount of current from resonant circuit 13 and provides it to lamp 5, 6232-107.CN -6-/lp/#11 203~05~
adding to the current flow therethrough a do component selected to minimize striations and anode oscillations.
Fig. 2A shows the ac component of current flow through a compact fluorescent lamp according to the present invention. The half period T is determined by frequency of the sinusoidal current and is preferably shorter than the recombination time of the gas plasma (~100~s) in order to sustain the electric discharge without flicker. The RMS
value of ac current to the lamp substantially determines the power and, therefore, the brightness of the lamp and is preferably adjustable from about 1 to 200 mA.
Fig. 2B shows the do component of current flow through the lamp. For illustrative purposes, the magnitude of the do component is exaggerated with respect to the ac component. As a practical matter, at full lamp power, the do component may range from about 0. 02 to 0 . 35 % of the ac component; at minimum lamp power, a do component of about 5% to 50% of the resultant current is preferred.
Fig. 2C shows the total current waveform that flows through the lamp. The do component offsets the ac component from the zero current level, causing a slightly asymmetric resultant current waveform that substantially reduced lamp striations.
Fig. 3 is a circuit schematic of the dimming circuit of the present invention. The circuit operates as follows: ac voltage is provided from a power source across hot (H) to neutral (N). Diodes D1 and D2, resistor R1, capacitors C1 and C2, and zener diode Z1 comprise a low voltage do power supply. During each positive voltage half-cycle, current flows from hot through capacitors C1 and C2, and diode D2 to neutral, charging capacitor C2 plus(+) to minus(-), as shown. Resistor R1 and zener diode Z1 regulate the voltage on capacitor C2 so that the power supply is essentially a do voltage source having a do supply voltage equal to the breakover voltage of zener diode Z1 and an internal resistance essentially equal to 6232-107.CN -7-/lp/#11 20~2(~~~
R1. Diode D1 provides a discharge path for capacitor C1 during each negative voltage half-cycle.
Full-wave-bridge FWB rectifies ac voltage from the power source and provides pulsating do voltage across the output terminals (+) and (-). Pulsating do is filtered by capacitor C3, which is connected across the output ter-minals of the full-wave-bridge. Resistor R2 is connected in parallel with C3 and bleeds charge from it when power is removed. For purposes of this specification and the appended claims, when referring to electrical elements, the term "connected°' means that there exists between two or more elements a conductive path, which may include addi-tional elements not explicitly recited.
Diodes D3, D~, D5, and D6, MOSFETS Q1 and Q2, resistors R3 and R4, transformer T1, and capacitor C4 comprise a switching inverter for switching and inverting filtered do voltage into a high-frequency ac driving voltage. During operation, capacitor C4 charges up to approximately half of the voltage across capacitor C3.
When Q1 is conductive, a driving voltage is applied across the primary winding P of transformer T2 that is positive and equal to the voltage across C3 less the voltage across C3 less the voltage across C4 (approximately half the voltage across C3). When Q2 is conductive, the driving voltage is inverted and equal to the voltage across C4.
When Q1 and Q2 are alternately switched at a high-frequency (~27kHz), rectangular pulses of ac driving voltage are produced having a peak-to-peak voltage substantially equal to the voltage across capacitor C3.
The driving frequency is preferably between 20kHz and 50kHz and is determined by the ac control voltage from the PDM circuit, IC1, discussed below. Frequencies below 20kHz are in the human audible range and are therefore undesirable. High frequencies above 50kHz are undesirable because they tend to cause high thermal dissipation in 6232-107.CN -8-/lp/#11 203~;0~8 MOSFETS Q1 and Q2 and they lower the capacitive impedance of the fixture wires to ground.
Resistors R3 and R4 damp oscillations which may otherwise occur due to the leakage inductance of secondary windings S1 and S2 of transformer T1 and gate capacitance of MOSFETS Q1 and Q2. Diodes D3 and D4 block reverse current from flowing through MOSFETS Q1 and Q2, respective-ly. Diodes D5 and D6 provide a commutation path for current flowing through Q2 and Q1, respectively.
Q1 and Q2 could be any type of semiconductor switch, such as FETS or bipolar transistors: however, MOSFETS, as shown, are preferred because of their fast switching ability and their relatively iow gate current requirements. Alternatively, the switching inverter may be replaced with a less-expensive semiconductor do frequency converter, which converts a non-pulsating do voltage into a high-frequency pulsating do voltage. An inverting type of oscillating circuit, which converts do to ac, is preferred, however, since it provides reduced peak magnetic flux in the core of the power-carrying transformers for the same amount of transformed energy.
Pulse duration modulation circuit PDM receives voltage (+VDC) from the do power supply and provides an ac control voltage across the primary winding P of transformer T1 to control the conductivity of MOSFETS Q1 and Q2 and, accordingly, the duration of each rectangular pulse of driving voltage. Secondary windings S1 and S2 of trans-former T1 are arranged so that voltage is applied to the gates of MOSFETS Q1 and Q2 in opposite polarities so that only one device may be conductive at any given time.
Pulse-duration-modulated driving voltage is provided across primary P of transformer T2 and across the resonant circuit consisting of inductor L1 and capacitor C5 connected in series. The resonant circuit rings substantially sinusoid-ally at the driving frequency with an amplitude determined by the pulse duration of the driving voltage and the 6232-107.CN -9-/lp/#11 203~05~
magnification factor Q of the resonant circuit. The magnification factor Q, in this case, is determined primar-ily by the impedance of lamps FL1 and FL2, which load the resonant circuit in parallel.
Loading the resonant circuit in parallel tends to stabilize operation of the gas discharge lamps. In par-ticular, as current through the lamps increases, lamp impedance decreases, decreasing the magnification factor Q
of the resonant circuit and, thereby, reducing its resonant response. Conversely, as the current through the lamps decreases, lamp impedance increases, increasing the mag-nification factor Q of the resonant circuit and, thereby, boosting its resonant response. The resonant circuit essentially behaves like an ac current source and provides high-frequency sinusoidal current through transformer T3 to Lamps FL1 and FL2. The magnitude of the current is vari-able from about 1 to 200mA RMS, depending upon the pulse duration of the driving voltage, and is sufficient to strike and maintain an electric discharge in the lamps.
To further increase the stability of the resonant circuit, the frequency of the driving voltage (~27kHz) is less than the peak response frequency of the resonant circuit (~33kHz). Alternatively, damping could be added to the resonant circuit, reducing the magnification factor Q:
however, this would reduce its efficiency and generate unwanted heat.
Capacitor C6, resistors R5 and R6, and diode D7 form a back end rectifier circuit for providing do current through lamps FL1 and FL2 in series. Capacitor C6, con-nected between secondary windings S1 and S2 of transformer T3, is selected to pass substantially all high-frequency sinusoidal current from the resonant circuit to lamps FL1 and FL2. Resistor R6 allows do current to flow through diode D7, providing a do offset to capacitor C6 so that the sinusoidal current through C6 and lamps FL1 and FL2 re-ceives a do component of current, as determined by resistor 6232-107.CN -10-/lp/#11 2~3~,~5~
R6. Resistor R5 is essentially a bleeder to discharge capacitor C6 when power is removed. Resistor R5 also limits the amount of do offset on capacitor C6 when the impedance of the lamps increases (at low power levels).
Earth ground is referenced between secondary windings S1 and S2 of transformer T3. The relative sizes of the secondary windings are selected to provide suffi-cient voltage with respect. to ground to strike lamps FL1 and FL2 through the capacitance to ground of each lamp.
They are also selected to balance the ground currents through each lamp so that the high-frequency sinusoidal current energizes the lamps equally. In this particular circuit, a compromise is necessary to achieve sufficient striking voltage and, thus, the ground current through lamp FL1 is slightly larger than that through FL2. To correct for this imbalance, capacitor C7 is provided in shunt with lamp FL1 to provide compensating current to lamp FL2.
Capacitor C8 prevents high-frequency switching noise from MOSFETS Q1 and Q2 in the switching inverter from adversely affecting the light output of lamps FL1 and FL2.
Secondary windings S1, S2, and S3 of transformer T2 provide voltage to the filaments of lamps FL1 and FL2 to heat them. Primary winding P of transformer T2 receives pulse-duration-modulated voltage from the switching in-verter circuit including MOSFETS Q1 and Q2. In addition, after Q1 is turned off and before Q2 is turned on, current through Q1 and inductor L1 commutates through diode D6, turning it on. This provides across primary winding P of transformer T2 an additional pulse of voltage, having an amplitude equal to the voltage across capacitor C4. Once the voltage across capacitor C5 reaches its peak, current reverses through inductor L1, and capacitor C5 discharges, turning diode D5 on. This provides across primary winding P a second pulse of voltage, having an amplitude equal and opposite to that of the first pulse. The two additional voltage pulses substantially occupy the period of time 6232-107.CN -11-/lp/#11 ~0320~~
after Q1 is turned off and before Q2 is turned on. The circuit behaves similarly during the period after Q2 is turned off and before Q1 is turned on. The resultant high-frequency voltage across primary winding P has an Ri~IS
value that is substantially constant throughout the dimming range of the lamps. Thus, secondary windings S1, S2, and S3 also provide constant RMS voltage to heat the filaments of lamps FL1 and FL2 throughout the dimming range.
Although the present invention is described for use with compact fluorescent lamps, the circuit herein descri bed may be used to control any type of gas discharge lamp.
Since certain changes may be made in the above described circuits without departing from the scope of the invention herein involved, it is intended that all matter contained in the above description or shown in the accompanying drawings shall be interpreted in an illustrative and not a limiting sense.
6232-107.CN -12-/lp/#11
CIRCUIT FOR DIMMING GAS DISCHARGE
LAMPS WITHOUT INTRODUCING STRIATIONS
Background of the Invention Field of the Invention This invention pertains to dimming gas discharge lamps and, more particularly, to dimming compact fluores-cent lamps.
Description of the Related Axt A gas discharge lamp converts electrical energy into visible energy with high efficiency. A gas discharge lamp is generally an elongated gas-filled (usually low pressure mercury vapor) tube having electrodes at each end.
Each electrode is formed from a resistive filament (usually tungsten) coated with a thermionically emissive material, such as a mixture of alkaline earth oxides.
The steady-state operation of a gas discharge lamp is as follows: Voltage is applied across the resistive filaments, heating the electrodes to a temperature suffi-cient to cause thermionic emission of electrons into the discharge tube. A voltage applied between the electrodes accelerates the electrons toward the anode. En route to the anode, the electrons collide with gas atoms to produce positive ions and additional electrons, forming in the tube a gas plasma of positive and negative charge carriers. The electrons continue to stream toward the anode and the 6232-107.CN -1-/lp/#11 positive ions toward the cathode, sustaining an electric discharge in the tube and further heating the electrodes.
(If the applied power is ac, the electrodes reverse polar-ity during each half cycle.) The discharge causes the emission of radiation having a wavelength dependent upon the particular fill gas and the electrical parameters of the discharge. Because each collision produces additional electrons and ions, increases in the arc current can cause the impedance of the lamp to decrease, a characteristic known as "negative resistance." Operation of the lamp is inherently unstable, due to this negative resistance characteristic, and current between the electrodes must be limited by external means to avoid damaging the lamp.
Dimming of gas discharge lamps is well known. A
circuit for dimming conventional fluorescent gas discharge lamp is disclosed in U.S. Patent No. 3,927,345, issued December 16, 1975, to Licata et al. A fluorescent lamp is a gas discharge lamp in which the inner surface of the tube is coated with a fluorescent phosphor. The phosphor is excited by ultraviolet radiation from the electric discharge and fluoresces, providing visible light. Licata discloses a phase control dimming circuit which provides phase controlled voltage from a 60Iiz ac source to a fluorescent lamp in series with an inductive ballast. The dimxcir~g . circuit employs a bidirectional triode-type thyristor (triac) as the main switching device and includes a ~c compensation circuit to ensure symmetrical triac firing delays in each half cycle of power flow from the ac source: There is no current through the lamp during the triac firing delay. Symmetrically firing the triac prevents excessive amount of do current from flowing through the lamp, which can cause lamp flickering and saturation of the inductive ballast. The circuit operates over a dimming range from about 100% to 50~ of full light output. Below about 500 light output, 6232-107.CN -2-/ 1 p/'~ 11 ~o~~~~~
the electrical discharge cannot be sustained, because the triac firing delay is longer than the recombination time of the gas plasma in the discharge tube.
U.S. Patent No. 4,001,637 issued January 4, 1977, to Gray, discloses a gas discharge Iamp dimming circuit that is capable of operating lamps at dimming levels below 50% of full light output. how dimming levels are attained by providing uninterrupted filtered do current to the lamp.
The circuit includes a capacitative ballast, a full wave rectifier, and an output filter. Ac current flows from a phase controlled source through the capacitive ballast to a full-wave rectifier. Pulsating do current is provided by the full-wave rectifier to an LC low pass filter and then to the lamp electrodes. However, do current tends to cause anode oscillations, uneven illumination along the length of the lamp, and a reduction in useful lamp life.
Anodes oscillations can be greatly reduced by operating a lamp at frequencies much higher than the fundamental frequency of the anode oscillation. U.S.
Patent No. 4,207,498, issued June 10, 1980, to Spires et al., discloses a dimming system that includes a central inverter for providing a 23kHz ac current through the lamp.
The lamp can be dimmed over a range form 100% to 1% of full light output by adjusting the amplitude of the inverter output. The use of high-frequency ac current also may increase the efficacy of the lamp by as much as 20%.
At low light levels (less than about 30% of full light output), however, the lamp tends to '°striate"; i.e., to break up into alternating bands of bright and dim areas along the length of the tube. The mechanisms that cause striation are not completely understood, but it is believed to result from high-frequency currents reinforcing a standing wave of varying charge distribution between the lamp electrodes. For reasons that are not clear, small-diameter lamps and lamps with sharp bends (typical charac-6232-107.CN -3-/lp/#11 zo3;Do~s teristics of compact fluorescent lamps) are more likely to striate.
Summary of the Invention The present invention provides a dimming control circuit for compact fluorescent lamps which greatly reduces striation while maintaining a flicker-free dimming range from about 1000 to 1~ of full light output. The dimming circuit generally provides 27kHz sinusoidal current to the lamp electrodes to initiate and maintain an electric discharge through the lamp and, simultaneously, provides a small amount of substantially non-pulsating do current to the electrodes to produce an asymmetric current waveform through the lamp. The asymmetric currant flow greatly reduces visible striations in the lamp. We believed that asymmetry alters the charge distribution in the tube to prevent formation of a standing wave between the lamp electrodes. Although a wave-like variation in charge distribution can be measured along the discharge tube, it is not a standing wave; it moves with a velocity that is determined by the magnitude of the do component of current flow through the lamp. Visible striations are eliminated by providing to the lamps a do current that causes the bright and dim bands, produced by the wave-like charge distribution, to move rapidly, so they become impercep-tible. Too much do current, however, causes anode oscil-lations. A suitable amount of do current is selected by compromising between the effects of striations and anode oscillations. It has been .found experimentally that a do current of about .04 to l.4mA satisfactorily achieves this compromise for a typical compact fluorescent lamp. Genera-lly, the optimum do current increases over the dimming range between minimum and mid range power. At higher powers, the precise value of do current is less critical.
The ratio of do current in the low-to-mid range is prefer-ably about 1:2. Thus, preferred do currents axe about 0.04 6232-107.CN -4-/lp/#11 2~32~65~
to 0.7mA and about 0.1 to l.4mA at minimum and half-maximum lamp powers, respectively.
According to the present invention, a control system for providing electrical power from a source to a gas discharge lamp comprises:
a) means fox providing symmetrical ac current to the electrodes of said lamp to strike and maintain an electric discharge therethrough; and b) means for simultaneously providing do current to said lamp electrodes;
whereby an asymmetric current waveform is established in the lamp, substantially eliminating the occurrence of visible striations.
In another embodiment of the present invention, a i5 control system for providing electrical power from a source to a pair of gas discharge lamps connected in series comprises:
a) means for providing symmetrical ac current to the electrodes of said lamps to strike and maintain an electric discharge therethrough; and b) means for simultaneously providing do current to said lamp electrodes;
whereby an asymmetric current waveform is established in the lamps, substantially eliminating the occurrence of visible striations.
Brief Description of the Drawings Fig. 1 is a block diagram of a dimming circuit of the present invention.
Fig. 2 is a graph of current flow through a compact fluorescent lamp according to the present invention.
Fig. 3 is a circuit schematic of a dimming circuit of the present invention.
6232-107.CN -5-/lp/#11 2p3~?05~
Detailed Description of the Present Invention Fig. 1 shows a block diagram of the dimming circuit of the present invention. The dimming circuit 1, enclosed in the dashed lines, provides a variable amount of power from sinusoidal power source 3 to a gas discharge lamp 5.
The dimming circuit generally includes a front-end rec-tifier 7 to convert a (typically) 60Hz ac voltage from power source 3 into a do voltage provided to switching inverter 9. Switching inverter 9 converts the do voltage into a high-frequency ac voltage consisting of alternately inverted and non-inverted rectangular pulses of voltage having variable duration. Pulse duration modulation (PDM) circuit 11 provides a modulating voltage waveform to switching inverter 9 to control the duration of each pulse.
The high-frequency ac voltage from switching inverter 9 drives resonant circuit 13 so that it resonates substantially sinusoidally, with an amplitude determined by the amplitude and frequency of the driving voltage and the magnification factor Q of the resonant circuit. The resonant circuit is essentially a symmetrical high-frequen-cy sinusoidal current source with a variable amplitude determined by the pulse duration of the driving voltage from switching inverter 9. In this specification and the appended claims, a resonant circuit is understood to have a single fundamental mode of resonance. The term "peak response frequency" refers to the frequency at which this fundamental resonance is maximized. As applied to ac waveforms, the term °'symmetrical" is understood to mean that the positive portion of the waveform is substantially identical in shape and magnitude to the corresponding negative portion of the waveform.
The current from resonant circuit 13 is provided to lamp 5 to strike and maintain a stable electric discharge over a range of selectable power levels. Simultaneously, back-end rectifier 15 rectifies a predetermined amount of current from resonant circuit 13 and provides it to lamp 5, 6232-107.CN -6-/lp/#11 203~05~
adding to the current flow therethrough a do component selected to minimize striations and anode oscillations.
Fig. 2A shows the ac component of current flow through a compact fluorescent lamp according to the present invention. The half period T is determined by frequency of the sinusoidal current and is preferably shorter than the recombination time of the gas plasma (~100~s) in order to sustain the electric discharge without flicker. The RMS
value of ac current to the lamp substantially determines the power and, therefore, the brightness of the lamp and is preferably adjustable from about 1 to 200 mA.
Fig. 2B shows the do component of current flow through the lamp. For illustrative purposes, the magnitude of the do component is exaggerated with respect to the ac component. As a practical matter, at full lamp power, the do component may range from about 0. 02 to 0 . 35 % of the ac component; at minimum lamp power, a do component of about 5% to 50% of the resultant current is preferred.
Fig. 2C shows the total current waveform that flows through the lamp. The do component offsets the ac component from the zero current level, causing a slightly asymmetric resultant current waveform that substantially reduced lamp striations.
Fig. 3 is a circuit schematic of the dimming circuit of the present invention. The circuit operates as follows: ac voltage is provided from a power source across hot (H) to neutral (N). Diodes D1 and D2, resistor R1, capacitors C1 and C2, and zener diode Z1 comprise a low voltage do power supply. During each positive voltage half-cycle, current flows from hot through capacitors C1 and C2, and diode D2 to neutral, charging capacitor C2 plus(+) to minus(-), as shown. Resistor R1 and zener diode Z1 regulate the voltage on capacitor C2 so that the power supply is essentially a do voltage source having a do supply voltage equal to the breakover voltage of zener diode Z1 and an internal resistance essentially equal to 6232-107.CN -7-/lp/#11 20~2(~~~
R1. Diode D1 provides a discharge path for capacitor C1 during each negative voltage half-cycle.
Full-wave-bridge FWB rectifies ac voltage from the power source and provides pulsating do voltage across the output terminals (+) and (-). Pulsating do is filtered by capacitor C3, which is connected across the output ter-minals of the full-wave-bridge. Resistor R2 is connected in parallel with C3 and bleeds charge from it when power is removed. For purposes of this specification and the appended claims, when referring to electrical elements, the term "connected°' means that there exists between two or more elements a conductive path, which may include addi-tional elements not explicitly recited.
Diodes D3, D~, D5, and D6, MOSFETS Q1 and Q2, resistors R3 and R4, transformer T1, and capacitor C4 comprise a switching inverter for switching and inverting filtered do voltage into a high-frequency ac driving voltage. During operation, capacitor C4 charges up to approximately half of the voltage across capacitor C3.
When Q1 is conductive, a driving voltage is applied across the primary winding P of transformer T2 that is positive and equal to the voltage across C3 less the voltage across C3 less the voltage across C4 (approximately half the voltage across C3). When Q2 is conductive, the driving voltage is inverted and equal to the voltage across C4.
When Q1 and Q2 are alternately switched at a high-frequency (~27kHz), rectangular pulses of ac driving voltage are produced having a peak-to-peak voltage substantially equal to the voltage across capacitor C3.
The driving frequency is preferably between 20kHz and 50kHz and is determined by the ac control voltage from the PDM circuit, IC1, discussed below. Frequencies below 20kHz are in the human audible range and are therefore undesirable. High frequencies above 50kHz are undesirable because they tend to cause high thermal dissipation in 6232-107.CN -8-/lp/#11 203~;0~8 MOSFETS Q1 and Q2 and they lower the capacitive impedance of the fixture wires to ground.
Resistors R3 and R4 damp oscillations which may otherwise occur due to the leakage inductance of secondary windings S1 and S2 of transformer T1 and gate capacitance of MOSFETS Q1 and Q2. Diodes D3 and D4 block reverse current from flowing through MOSFETS Q1 and Q2, respective-ly. Diodes D5 and D6 provide a commutation path for current flowing through Q2 and Q1, respectively.
Q1 and Q2 could be any type of semiconductor switch, such as FETS or bipolar transistors: however, MOSFETS, as shown, are preferred because of their fast switching ability and their relatively iow gate current requirements. Alternatively, the switching inverter may be replaced with a less-expensive semiconductor do frequency converter, which converts a non-pulsating do voltage into a high-frequency pulsating do voltage. An inverting type of oscillating circuit, which converts do to ac, is preferred, however, since it provides reduced peak magnetic flux in the core of the power-carrying transformers for the same amount of transformed energy.
Pulse duration modulation circuit PDM receives voltage (+VDC) from the do power supply and provides an ac control voltage across the primary winding P of transformer T1 to control the conductivity of MOSFETS Q1 and Q2 and, accordingly, the duration of each rectangular pulse of driving voltage. Secondary windings S1 and S2 of trans-former T1 are arranged so that voltage is applied to the gates of MOSFETS Q1 and Q2 in opposite polarities so that only one device may be conductive at any given time.
Pulse-duration-modulated driving voltage is provided across primary P of transformer T2 and across the resonant circuit consisting of inductor L1 and capacitor C5 connected in series. The resonant circuit rings substantially sinusoid-ally at the driving frequency with an amplitude determined by the pulse duration of the driving voltage and the 6232-107.CN -9-/lp/#11 203~05~
magnification factor Q of the resonant circuit. The magnification factor Q, in this case, is determined primar-ily by the impedance of lamps FL1 and FL2, which load the resonant circuit in parallel.
Loading the resonant circuit in parallel tends to stabilize operation of the gas discharge lamps. In par-ticular, as current through the lamps increases, lamp impedance decreases, decreasing the magnification factor Q
of the resonant circuit and, thereby, reducing its resonant response. Conversely, as the current through the lamps decreases, lamp impedance increases, increasing the mag-nification factor Q of the resonant circuit and, thereby, boosting its resonant response. The resonant circuit essentially behaves like an ac current source and provides high-frequency sinusoidal current through transformer T3 to Lamps FL1 and FL2. The magnitude of the current is vari-able from about 1 to 200mA RMS, depending upon the pulse duration of the driving voltage, and is sufficient to strike and maintain an electric discharge in the lamps.
To further increase the stability of the resonant circuit, the frequency of the driving voltage (~27kHz) is less than the peak response frequency of the resonant circuit (~33kHz). Alternatively, damping could be added to the resonant circuit, reducing the magnification factor Q:
however, this would reduce its efficiency and generate unwanted heat.
Capacitor C6, resistors R5 and R6, and diode D7 form a back end rectifier circuit for providing do current through lamps FL1 and FL2 in series. Capacitor C6, con-nected between secondary windings S1 and S2 of transformer T3, is selected to pass substantially all high-frequency sinusoidal current from the resonant circuit to lamps FL1 and FL2. Resistor R6 allows do current to flow through diode D7, providing a do offset to capacitor C6 so that the sinusoidal current through C6 and lamps FL1 and FL2 re-ceives a do component of current, as determined by resistor 6232-107.CN -10-/lp/#11 2~3~,~5~
R6. Resistor R5 is essentially a bleeder to discharge capacitor C6 when power is removed. Resistor R5 also limits the amount of do offset on capacitor C6 when the impedance of the lamps increases (at low power levels).
Earth ground is referenced between secondary windings S1 and S2 of transformer T3. The relative sizes of the secondary windings are selected to provide suffi-cient voltage with respect. to ground to strike lamps FL1 and FL2 through the capacitance to ground of each lamp.
They are also selected to balance the ground currents through each lamp so that the high-frequency sinusoidal current energizes the lamps equally. In this particular circuit, a compromise is necessary to achieve sufficient striking voltage and, thus, the ground current through lamp FL1 is slightly larger than that through FL2. To correct for this imbalance, capacitor C7 is provided in shunt with lamp FL1 to provide compensating current to lamp FL2.
Capacitor C8 prevents high-frequency switching noise from MOSFETS Q1 and Q2 in the switching inverter from adversely affecting the light output of lamps FL1 and FL2.
Secondary windings S1, S2, and S3 of transformer T2 provide voltage to the filaments of lamps FL1 and FL2 to heat them. Primary winding P of transformer T2 receives pulse-duration-modulated voltage from the switching in-verter circuit including MOSFETS Q1 and Q2. In addition, after Q1 is turned off and before Q2 is turned on, current through Q1 and inductor L1 commutates through diode D6, turning it on. This provides across primary winding P of transformer T2 an additional pulse of voltage, having an amplitude equal to the voltage across capacitor C4. Once the voltage across capacitor C5 reaches its peak, current reverses through inductor L1, and capacitor C5 discharges, turning diode D5 on. This provides across primary winding P a second pulse of voltage, having an amplitude equal and opposite to that of the first pulse. The two additional voltage pulses substantially occupy the period of time 6232-107.CN -11-/lp/#11 ~0320~~
after Q1 is turned off and before Q2 is turned on. The circuit behaves similarly during the period after Q2 is turned off and before Q1 is turned on. The resultant high-frequency voltage across primary winding P has an Ri~IS
value that is substantially constant throughout the dimming range of the lamps. Thus, secondary windings S1, S2, and S3 also provide constant RMS voltage to heat the filaments of lamps FL1 and FL2 throughout the dimming range.
Although the present invention is described for use with compact fluorescent lamps, the circuit herein descri bed may be used to control any type of gas discharge lamp.
Since certain changes may be made in the above described circuits without departing from the scope of the invention herein involved, it is intended that all matter contained in the above description or shown in the accompanying drawings shall be interpreted in an illustrative and not a limiting sense.
6232-107.CN -12-/lp/#11
Claims (21)
1. A control system for providing electrical power from a source to a gas discharge lamp, the gas discharge lamp having a lamp power variable between a maximum and a minimum, the control system comprising:
(a) means for providing symmetrical ac current to the electrodes of said lamp to strike and maintain and electric discharge therethrough; and (b) means for simultaneously providing do current to said lamp electrodes; whereby an asymmetric current waveform is established in the lamp, substantially eliminating the occurrence of visible striations, said dc current comprising approximately between 0.02% and 0.35% of the resultant current through said lamp at maximum lamp power and approximately between 5% and 50% of the resultant current through said lamp at minimum lamp power.
(a) means for providing symmetrical ac current to the electrodes of said lamp to strike and maintain and electric discharge therethrough; and (b) means for simultaneously providing do current to said lamp electrodes; whereby an asymmetric current waveform is established in the lamp, substantially eliminating the occurrence of visible striations, said dc current comprising approximately between 0.02% and 0.35% of the resultant current through said lamp at maximum lamp power and approximately between 5% and 50% of the resultant current through said lamp at minimum lamp power.
2. The control system of claim 1 wherein said ac current providing means comprises a resonant circuit including an inductor and a capacitor connected in series.
3. The control system of claim 2 wherein said ac current providing means further comprises a switching inverter, including at least one semiconductor switch, to drive said resonant circuit.
4. The control system of claim 3 wherein said semiconductor switch comprises a MOSFET.
5. The control system of claim 2 wherein said ac current providing means further comprises a transformer connected between said resonant circuit and said lamp.
6. The control system of claim 1 wherein said ac current is approximately between 20kHz and 50kHz.
7. The control system of claim 1 wherein said ac current providing means comprises a dc current source connected in parallel with said ac current providing means.
8. The control system of claim 1 wherein said dc current providing means comprises a rectifying circuit for rectifying a predetermined portion of said ac current.
9. The control system of claim 1 wherein said do current is between about 0.04 and 0.7mA at minimum lamp power and between about 0.1 and 1.4 mA at about half maximum lamp power.
10. The control system of claim 1 wherein said ac current providing means comprises a transformer, including two secondary windings connected in series with each other and said lamp; and said do current providing means comprises a capacitor electrically connected between said secondary windings and a first resistor and a diode connected in series across one of said secondary windings.
11. The control system of claim 10 wherein said do current means further comprises a second resistor connected in parallel with said capacitor.
12. A control system for providing electrical power from a source to a pair of gas discharge lamps connected in series, each of said discharge lamps having a lamp power variable between a maximum and a minimum, the control system comprising:
(a) means for providing symmetrical ac current to the electrodes of said lamps to strike and maintain an electric discharge therethrough; and (b) means for simultaneously providing dc current to said lamp electrodes; whereby an asymmetric current waveform is established in the lamps, substantially eliminating the occurrence of visible striations, said dc current comprising approximately between 0.02% and 0.35% of the resultant current through said lamp at maximum lamp power and approximately between 5% and 50% of the resultant current through said lamp at minimum lamp power.
(a) means for providing symmetrical ac current to the electrodes of said lamps to strike and maintain an electric discharge therethrough; and (b) means for simultaneously providing dc current to said lamp electrodes; whereby an asymmetric current waveform is established in the lamps, substantially eliminating the occurrence of visible striations, said dc current comprising approximately between 0.02% and 0.35% of the resultant current through said lamp at maximum lamp power and approximately between 5% and 50% of the resultant current through said lamp at minimum lamp power.
13. The control system of claim 12 wherein said ac current providing means comprises a resonant circuit including an inductor and a capacitor connected in series.
14. The control system of claim 13 wherein said ac current providing means further comprises a transformer, having a primary winding and two secondary windings, connected between said resonant circuit and said lamp.
15. The control system of claim 14 wherein said secondary windings are connected in series with each other and said lamps, and the connecting point between said secondary windings is connected to earth ground.
16. The control system of claim 15 wherein the relative number of turns on each of said secondary windings is selected to provide substantially equal currents to ground through each of said lamps.
17. The control system of claim 12 further comprising a capacitor connected in parallel with one of said lamps to provide substantially equal current flow to ground through each of said lamps.
18. The control system of claim 12 wherein said ac current is approximately between 20kHz and 50kHz.
19. The control system of claim 12 wherein said dc current providing means comprises a do current source connected in parallel with said ac current providing means.
20. The control system of claim 12 wherein said ac current providing means comprises a transformer, including two secondary windings connected in series with each other and said lamps; and said do current providing means comprises a capacitor connected between said secondary windings and a first resistor and a diode connected in series across one of said secondary windings.
21. The control system of claim 20 wherein the relative number of turns on each of said secondary windings is selected to provide substantially equal currents to ground through each of said lamps.
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| US07455644 US5001386B1 (en) | 1989-12-22 | 1989-12-22 | Circuit for dimming gas discharge lamps without introducing striations |
| US455,644 | 1989-12-22 |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CA2032058A1 CA2032058A1 (en) | 1991-06-23 |
| CA2032058C true CA2032058C (en) | 2000-04-18 |
Family
ID=23809669
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CA002032058A Expired - Lifetime CA2032058C (en) | 1989-12-22 | 1990-12-12 | Circuit for dimming gas discharge lamps without introducing striations |
Country Status (5)
| Country | Link |
|---|---|
| US (1) | US5001386B1 (en) |
| JP (1) | JP2892509B2 (en) |
| CA (1) | CA2032058C (en) |
| DE (1) | DE4039497A1 (en) |
| GB (1) | GB2239568B (en) |
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| US9681526B2 (en) | 2014-06-11 | 2017-06-13 | Leviton Manufacturing Co., Inc. | Power efficient line synchronized dimmer |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US3619716A (en) * | 1969-07-23 | 1971-11-09 | Lutron Electronics Co | High-frequency fluorescent tube lighting circuit and ac driving circuit therefor |
| US3731142A (en) * | 1971-08-20 | 1973-05-01 | Lutron Electronics Co | High-frequency fluorescent tube lighting circuit with isolating transformer |
| GB1358829A (en) * | 1972-07-13 | 1974-07-03 | Thorn Electrical Ind Ltd | Discharge lamp ballast circuits |
| US3904922A (en) * | 1973-11-19 | 1975-09-09 | Xerox Corp | Lamp control and lamp switch circuit |
| US4350935A (en) * | 1980-03-28 | 1982-09-21 | Lutron Electronics Co., Inc. | Gas discharge lamp control |
| FI65524C (en) * | 1982-04-21 | 1984-05-10 | Helvar Oy | FOER REFRIGERATION FOER MATNING AVERAGE REQUIREMENTS FOR FLUORESCENT LAMPS |
| US4663570A (en) * | 1984-08-17 | 1987-05-05 | Lutron Electronics Co., Inc. | High frequency gas discharge lamp dimming ballast |
| US4862042A (en) * | 1985-04-26 | 1989-08-29 | Herrick Kennan C | Apparatus and method for forming segmented luminosity in gas discharge tubes |
| US4682082A (en) * | 1985-05-16 | 1987-07-21 | The Scott & Fetzer Company | Gas discharge lamp energization circuit |
| US4663569A (en) * | 1985-09-26 | 1987-05-05 | General Electric Company | Energy management/dimming system and control |
| US4651060A (en) * | 1985-11-13 | 1987-03-17 | Electro Controls Inc. | Method and apparatus for dimming fluorescent lights |
| US4745342A (en) * | 1986-10-30 | 1988-05-17 | Andresen Jack S | Method and apparatus for driving neon tube to form luminous bubbles and controlling the movement thereof |
| US4870326A (en) * | 1986-10-30 | 1989-09-26 | Jack Andresen | Method and apparatus for driving neon tube to form luminous bubbles and controlling the movement thereof |
| US4792727A (en) * | 1987-10-05 | 1988-12-20 | Gte Products Corporation | System and method for operating a discharge lamp to obtain positive volt-ampere characteristic |
| US4853598A (en) * | 1987-10-13 | 1989-08-01 | Alexander Kusko | Fluorescent lamp controlling |
| US4916362A (en) * | 1988-04-05 | 1990-04-10 | Neon Dynamics Corporation | Excitation supply for gas discharge tubes |
| US5170099A (en) * | 1989-03-28 | 1992-12-08 | Matsushita Electric Works, Ltd. | Discharge lamp lighting device |
| US5144205A (en) * | 1989-05-18 | 1992-09-01 | Lutron Electronics Co., Inc. | Compact fluorescent lamp dimming system |
| DE3928809A1 (en) * | 1989-08-31 | 1991-03-07 | Philips Patentverwaltung | CIRCUIT ARRANGEMENT FOR FEEDING A LOAD |
-
1989
- 1989-12-22 US US07455644 patent/US5001386B1/en not_active Expired - Lifetime
-
1990
- 1990-12-11 DE DE4039497A patent/DE4039497A1/en not_active Ceased
- 1990-12-12 JP JP2410492A patent/JP2892509B2/en not_active Expired - Lifetime
- 1990-12-12 CA CA002032058A patent/CA2032058C/en not_active Expired - Lifetime
- 1990-12-12 GB GB9026930A patent/GB2239568B/en not_active Expired - Lifetime
Also Published As
| Publication number | Publication date |
|---|---|
| US5001386A (en) | 1991-03-19 |
| JP2892509B2 (en) | 1999-05-17 |
| GB2239568B (en) | 1994-06-08 |
| CA2032058A1 (en) | 1991-06-23 |
| GB9026930D0 (en) | 1991-01-30 |
| JPH04112494A (en) | 1992-04-14 |
| DE4039497A1 (en) | 1991-06-27 |
| US5001386B1 (en) | 1996-10-15 |
| GB2239568A (en) | 1991-07-03 |
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| EEER | Examination request | ||
| MKEX | Expiry |