CA1267438A - Electrosurgical generator with improved circuitry for generating rf drive pulse trains - Google Patents
Electrosurgical generator with improved circuitry for generating rf drive pulse trainsInfo
- Publication number
- CA1267438A CA1267438A CA000502333A CA502333A CA1267438A CA 1267438 A CA1267438 A CA 1267438A CA 000502333 A CA000502333 A CA 000502333A CA 502333 A CA502333 A CA 502333A CA 1267438 A CA1267438 A CA 1267438A
- Authority
- CA
- Canada
- Prior art keywords
- bit binary
- signal
- storage device
- memory locations
- generator
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Lifetime
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Classifications
-
- A—HUMAN NECESSITIES
- A61—MEDICAL OR VETERINARY SCIENCE; HYGIENE
- A61B—DIAGNOSIS; SURGERY; IDENTIFICATION
- A61B18/00—Surgical instruments, devices or methods for transferring non-mechanical forms of energy to or from the body
- A61B18/04—Surgical instruments, devices or methods for transferring non-mechanical forms of energy to or from the body by heating
- A61B18/12—Surgical instruments, devices or methods for transferring non-mechanical forms of energy to or from the body by heating by passing a current through the tissue to be heated, e.g. high-frequency current
- A61B18/1206—Generators therefor
-
- A—HUMAN NECESSITIES
- A61—MEDICAL OR VETERINARY SCIENCE; HYGIENE
- A61B—DIAGNOSIS; SURGERY; IDENTIFICATION
- A61B18/00—Surgical instruments, devices or methods for transferring non-mechanical forms of energy to or from the body
- A61B18/04—Surgical instruments, devices or methods for transferring non-mechanical forms of energy to or from the body by heating
- A61B18/12—Surgical instruments, devices or methods for transferring non-mechanical forms of energy to or from the body by heating by passing a current through the tissue to be heated, e.g. high-frequency current
-
- A—HUMAN NECESSITIES
- A61—MEDICAL OR VETERINARY SCIENCE; HYGIENE
- A61B—DIAGNOSIS; SURGERY; IDENTIFICATION
- A61B18/00—Surgical instruments, devices or methods for transferring non-mechanical forms of energy to or from the body
- A61B2018/00636—Sensing and controlling the application of energy
- A61B2018/0066—Sensing and controlling the application of energy without feedback, i.e. open loop control
-
- A—HUMAN NECESSITIES
- A61—MEDICAL OR VETERINARY SCIENCE; HYGIENE
- A61B—DIAGNOSIS; SURGERY; IDENTIFICATION
- A61B18/00—Surgical instruments, devices or methods for transferring non-mechanical forms of energy to or from the body
- A61B2018/00636—Sensing and controlling the application of energy
- A61B2018/00684—Sensing and controlling the application of energy using lookup tables
Abstract
ABSTRACT OF THE DISCLOSURE
An electrosurgical generator comprises a patient circuit which includes an active electrode and a return electrode. The generator generates a pulse train and includes an MXN storage device having M memory locations where M > 1 and each location having N storage positions where N ? 1. The storage device stores at least one K-bit binary signal which is sequentially put out from the storage device. An electrosurgical signal generating circuit which is response to the K-bit binary signal generates an electrosurgical signal which is applied to the patient circuit.
An electrosurgical generator comprises a patient circuit which includes an active electrode and a return electrode. The generator generates a pulse train and includes an MXN storage device having M memory locations where M > 1 and each location having N storage positions where N ? 1. The storage device stores at least one K-bit binary signal which is sequentially put out from the storage device. An electrosurgical signal generating circuit which is response to the K-bit binary signal generates an electrosurgical signal which is applied to the patient circuit.
Description
This invention relates to elec~rosurgical generators and in particular to improved circu:Ltry Eor generating RF dri-ve puLse tra:Lns ln such generators.
With the increase in operating modes of electrosurgical generators (for example, four CUT and two COAG modes), the need to efficiently generate these wave shapes both in terms oE cost and parts count is becoming increasingly important. Typically a substantial number of integrated circuits and an associated printed circuit card are presently dedicated to the generation oE RF ON and RF OFF drive pulses. In reducing the cost of such electrosurgical generators it is important the foregoing circuitry be substantially reduced.
It is accordingly a primary object of this invention to provide pulse generating circuits for use in electrosurgical generators which substantially reduce the complexity and cost thereof.
The foregoing is implemented by using shift registers and other storage devices such as P~OM's in a novel manner in electrosurgical generators -to effect the desired pulse generation. Although pulse ~ generators using storage devices of the above type have been employed in ; ~ other applications, their employment in the manner described hereina~ter in electrosurgical generators is novel.
The invention may be summarized as an electrosurgical generator comprising a patient circuit including an active electrode and a return electrode; and means for generating a pulse train in said generator, characterized in that said pulse train generating means includes at least one MXN storage device having M memory locations where M > 1 and where each location contains N storage positions where N ~ 1, said storage device storing at least one, K-bit blnary signal, where l~CK ~M bits of which are respective:Ly storecl in the Jth storage positions of K oE the M memory - 1 ~
.~. ' ,, :
,;: . ~
~ .
~ t~
locations where J ~; means for sequent:Lally outputting said K-bit binary signal ~rom said storage devlce; and electrosurgical s:ignal generating means responsive to the K-bit binary signal Eor generating an electrosurgical signal and applying this signal to the patient circuit.
The invention will now be described in greater detail with reference to the accompanying drawings.
- la -.
.
BRIEF DESCRIP~ION O~ THE DRAWIlilG
Fig. 1 is a partial sehematic, partial bloc~;
diagram of an illustrative electrosurgical generatirlg system in accordance with the invention.
~ig. 2 is a block diagram of a first embodiment of an illustrative pulse generator ~or use in the systern of Fi~ . 1 utilizing a f ixed length shif t regis-~er in accordance with the invention~
Pig. 3 depicts a plurality of waveforms which il~ustrate ~he operation of the Fi~. 2 embodimen~
Fig. 4 is a block diagram of a second em~odiment of an illustrati~e pulse generator for use in the system of Fig r 1 utilizing variable length shift regis-ters in accordance with the invention.
Fig. 5 is a block diagram of a third embodiment of an ilustrative pulse generator for use in the system of Fig~ 1 utilizin~ a pro~rammable memory in : accordance wi~h the invention.
. Fig~ 6 depicts data stored in the pr~gramma~le
With the increase in operating modes of electrosurgical generators (for example, four CUT and two COAG modes), the need to efficiently generate these wave shapes both in terms oE cost and parts count is becoming increasingly important. Typically a substantial number of integrated circuits and an associated printed circuit card are presently dedicated to the generation oE RF ON and RF OFF drive pulses. In reducing the cost of such electrosurgical generators it is important the foregoing circuitry be substantially reduced.
It is accordingly a primary object of this invention to provide pulse generating circuits for use in electrosurgical generators which substantially reduce the complexity and cost thereof.
The foregoing is implemented by using shift registers and other storage devices such as P~OM's in a novel manner in electrosurgical generators -to effect the desired pulse generation. Although pulse ~ generators using storage devices of the above type have been employed in ; ~ other applications, their employment in the manner described hereina~ter in electrosurgical generators is novel.
The invention may be summarized as an electrosurgical generator comprising a patient circuit including an active electrode and a return electrode; and means for generating a pulse train in said generator, characterized in that said pulse train generating means includes at least one MXN storage device having M memory locations where M > 1 and where each location contains N storage positions where N ~ 1, said storage device storing at least one, K-bit blnary signal, where l~CK ~M bits of which are respective:Ly storecl in the Jth storage positions of K oE the M memory - 1 ~
.~. ' ,, :
,;: . ~
~ .
~ t~
locations where J ~; means for sequent:Lally outputting said K-bit binary signal ~rom said storage devlce; and electrosurgical s:ignal generating means responsive to the K-bit binary signal Eor generating an electrosurgical signal and applying this signal to the patient circuit.
The invention will now be described in greater detail with reference to the accompanying drawings.
- la -.
.
BRIEF DESCRIP~ION O~ THE DRAWIlilG
Fig. 1 is a partial sehematic, partial bloc~;
diagram of an illustrative electrosurgical generatirlg system in accordance with the invention.
~ig. 2 is a block diagram of a first embodiment of an illustrative pulse generator ~or use in the systern of Fi~ . 1 utilizing a f ixed length shif t regis-~er in accordance with the invention~
Pig. 3 depicts a plurality of waveforms which il~ustrate ~he operation of the Fi~. 2 embodimen~
Fig. 4 is a block diagram of a second em~odiment of an illustrati~e pulse generator for use in the system of Fig r 1 utilizing variable length shift regis-ters in accordance with the invention.
Fig. 5 is a block diagram of a third embodiment of an ilustrative pulse generator for use in the system of Fig~ 1 utilizin~ a pro~rammable memory in : accordance wi~h the invention.
. Fig~ 6 depicts data stored in the pr~gramma~le
2~ memory of ~ig. 5 which illustrate the operation of the embodiment of ~ig. 5.
, . ~ " '' , .., ', ` -:
Fig. 1 illustrates an electrosurgical generator ~5 10 connected to a patient circuit including an active electro~e 12 for appl~ing -electrosurgical current to a patient and a return electrode 14 for returning the ~ current to the generator. The generator includes a : pulse generator 16 having an RF drive output which 3U con~titutes a pulse train of varying configurations . . . . . .
., _3_ .
~2~
depending upon the mode of operation of the generator, The RF drive is applied to a switch 18, which when closed connects a supply voltage 19 across a tank circuit 20 comprising a capacitoc 22 and a primary coil 24, the ~ank being transformer coupled to a coil 26 in the patient circuit. Typically the resonant frequency of the tank equals the fundamental frequency of the pulse train applied to switch 18 when the mode of operatisn is one of the CUT modes while the funda-mental frequeney of th~ RF drive is typically one-half that of the resonant frequency of he tank when the mode of operation is one of the two COAG modes. of course, the number of modes may vary as well as.th~
frequency relationship between that of the resonant frequency of the tank and the fundamen~al frequency of the RF drive, A first illustrative embodiment of the pulse gene-rator 16 of ~ 1 is shown in Fig. 2 and includes a fixed length shift register Ulr a flip-flop U2, OR
gates U3 and ~3A, AND gate pairs U4 and U4A, inver~ers ~5 and U5A, a NAND gate flip-flip U~B and a totem pole drive including FET's 30 and 32. The RF DRIVE output ~how~ in Fig. l corresponds to the ou~put of the totem pole drive of Fig. 2. It is assumed in the followin~
description of the Fi9. 2 embodiment, the fundamental frequency of the RF DRIVE pulse train is either 500 kHz or 2S0 kHz. The different wave drives for the four-CUT waveforms and the two-COAG waveforms consist of the modulation of these two clock frequencies at a : 30 multiple of their respective fundamental where a basic clock signal of 500 k~z is applied to terminal 34.
In order to derive the clock freguencies of 500 k9z or 250 kHz a FREQUENCY SELECT circuit indicated at 33 ls em-loyed. Thi- circuit includes tlip-flop U2 : .. ,, , , . , ~ . ,, :
, .. ' ~ '' . ...
~2~7~3~3 which is configured as a toggle flip-flop. Its output Q is one-half the 500 kHz input signal applied thereto and thus the output of the flip-flop is 250 kHz. The 500 kHz input pulse traln is generated by circuitry not shown in a known manner. A ~REQUENCY SELECT line 36 is directly cuupled to one of the two parallel AND
gates U4 and through an inverter U5 to the other of the parallel AND gates U4. The signal on the FREQUENCY
SELECT line is a simple on/off signal which may be either m'icroprocessor generate~ or hardware generated in a known manner. The outputs of AND circuits U4 are connected to an OR circuit U3. Thus, if the FREQUENCY
SELECT line 36 is held high the output of ~3 will be 250 kHz since the output of the flip-flop will be : 15 gated through the upper AND gate U4 to the OR circuit.
If the line 36 is held low, the output of ~3 will be ~00 kHz since the 500 k~z input signal to the flip-~lop is also applied to the lower AND gate U4 : where it is ~ated to the OR circuit. The output of ~3 is directly applied to a first one of an A~D gate pair ~4A while thP inverse thereo$ is applied to the second - AND.gate of the pair via an inverter ~5A. The second input to the AND gates U4A is the serial output of the fixed length shift register Ul.
~ 25 The shift register is parallel loaded with an : 8-bit word, which may be considered an RF mask. It is loaded when the SHIFT/LOAD line PIN 1 of the register is held low. This line will be held low when the inputs to QR circuit U3A are held low. This occurs when an externally generated CHIP SELECT signal (nega-tive true), CS, and a WRITE PULSE tagain negative true~, WR, are applied to the OR gate via terminals 40 and 42. Hence, the OR gate basically performs an AND
function in that both the CHIP SELECT and ~RITE PULSE
signals must be present before the data on data bus line 38 can be parallel loacled into the shift regis-ter. The OR gate U3A may be used to effect communica-tion between a microprocessor and the shift register.
Alternatively, a hardware generated pulse could also be applied to the SHIFT/LOAD line to load the RF
mask. The fcregoing is true in all embodiments of the invention. That is, external control si~nals can either be hardware generated or generated under micro-processor control.
Once the shi~t register is loaded, the infor-mation therein may be shifted out serially at a rate corresponding to the clock rate present at its CLOCK
input line PIN 2. In the present description, the frequency of the clock is 250 kHz since the Q output of U2 is connected to PIN 2 of the register and since it has been assumed a 500 kHz signal is applied to the toggle flip-flop. The ~5~ kHz clock is suitable for present electrosurgical generators; however, the fre-quency of the shift clocked signal could also be selec-table according to generator requirements. As the RF
mask is shifted out of the shift register at PI~ g thereof, it is also serially reloaded back into the register at PIN 10 thereof. Accordingly, the shift re-2S gister is reloaded wit~ the preloaded ~F mask such that the mask is continually shifted out and reloaded - in a bit-by-bit progression. The output of the shift register is then ANDed with the fundamental clock frequency at the parallel gates of U4A~ The two clock signals, RF ON and RF OFF, are generated at the outputs of these AND circuits where they respectively set and reset the flip-flop comprising NAND gates U5B.
The Q output of the flip-flop is used as the gate drive for the totem pole drive arran~ement of FET's 30 `` ; 6 and 32. The common drain point of the F~T's is out-putted as an on-off pulse train for the RF stage. This corresponds to the RF DRIVE outpu~ from generator 16 of Fig. 1.
The reset ~ate of the NAND flip-flop U5B will, in practice, typically have a third input (not shown) which can be used to shut an RF pulse off before the R~ pulse is generated. This can be used as a means of curren~ feedback or over voltage shutdown. That is, if excessive current is sensed in the output circuit including tank 20 by sensing means (not shown), the sensing mean~ will apply a signal to the above mention-ed third input to effectively decrease the current in the output circuit in the manner described above. If other means are employed to compensate for over volt-age in the output circuit only the R~ ON DRIVE pulses need be generated where these may be directly applied ~o switch 18 of Fig. 1. In this instance, the NAND
gate flip-flop and the totem pole drive may be elimin-ated. The foregoing also applies to the remaining embodiments of the invention.
It should also be noted an edge coupler or dif-ferentiator tnoS shown) may typically be employed at the SET input to the flip-flop uSB so that the flip-flop is set by a short duration pulse. The above circuit elements have not been shown to simplify the explanation of the invention.
Typical integrated circuits which may be employed to implement the circuitry of Fig. 2 are as follows, it being understood these circuits are but illus-trative: shift register Ul, a 74LS165; flip-flop ~2, a 74LS74, dual D-type 1ip-flop, U3 and U3A, a 74LS32, quadruple 2~input positive-OR gates; U4 and U4A, a 74LS08, quadruple 2-input positive-AND gates; and U5, U5A and U5B~ a 74L~00, ~uadxuple 2-input pOSitiVe-NAND
gates. All of the above circuits are described in the TTL-Databookl Second Edition by Texas Instruments. The FET totem pole drive arranyement may comprise a PNP-NPN eombination of FET's. Information on this com-bination can be found in tbe databook of the Int~rna-10 . tional Rectifier Company.
Reference should now be made to Fig. 3 which depicts variou~ timing wave shapes to illustrate the operation of the circuitry of ~ig. ~. In particular, thesP wave shapes result in a twenty-five percent modulated fundamental frequency of ~00 kHz at a modula-tion fre~uency of 31.25 kHz. Such an RF drive pulse train is illustrated as the upper most wave shape in Fig. 3. Beneath this wave shape is illustrated the RF
mask loacled into the shift register Vl where the FREQUENCY SELECT line is low - tha~ is, zero. The encircled num~ers adjacent the remaining waveforms occur at those points in the Fig. 2 circuit where similar encircled numbers are indicated. Thus, after the mask is loaded in the register, the leading edge of each clock pulse applied to shi~t register ~1 causes the register to be shlfted one sta~e and the last stage to be outputted at PIN 9. The shape of the signal occurring at the output o the register is accordingly as shown at ~ since only the first two bits of the mask are l's. This output signal from the register ~requency modulates the 500 kHZ signals applied to AND gates U4A to provide the RF ON and RF
OFF signals shown at ~ and 0 . These in turn set and reset the flip-flop to drive the totem pole arrange-~ . . .
ment so that the RF DRIVE output from the totem pole follows the gate input at ~ and thus the desired RY
DRIVE pulse train is effected.
Reference should now be made to Fig. 4 which is directed to a second embodiment of the invention, it being characterized by variable length shift registers ~2 and U3. The length of the shift registers is controlled by the binary data set in HEX D flip-flop Ul. A single gate U~ is used to generate a clock or 1~ latching pulse for flip-flop Ul. The data present on the data bus at the time of the occurrence of the write pulse W.R will be latched into the flip-flop if the CHIP SELECT signal, CS2, is also present. As soon as the data is l~tched into the flip-flop, the length of ~he shift registers U2 and ~3 will be set.
The length of the shift registers, whieh ma~ be from 1 to 64 bits, is preferrably equal ~o a multiple of ~he period of the output RF ON and ~F OFF drive pulse : trains. These pulse trains are shown at the outputs of the shift registers and correspond to the RF ON and R~
: OFF pulse trains occurring at the outputs of AND gates U4A in Fig. 2. Thus, the NAND gate flip-flop U5B and totem pole drive of Fig. 2 are not shown in Fig. 4 and in .the subseguent embodiments of this invention al-. 25 though it is to be understood the RF O~ and RF O~F
.
: pulse trains of the embodiment of Fig. 4 and the other .
embodiments of this invention could typically be - applied to a NAND gate flip-flop and totem pole drive in the same manner as is illustrated in Fig. 2.
The length of the shift registers should be equal to a multiple of the period of the output RF ON and RF
OFF pulse drive trains. Thus, for a simple on-off-on-off type repetitive drive, the length would be a . , ., ~ , ., ' . .. .
.
.
~;s~
multiple of two~ For a drive with a configuration of on-off-off-off and then repeating a~ain, the length would be a multiple of four~ The actual length is thus determined by how many periods of the output wave shape are loaded into the shift registers.
The shift registers U2 and U3 are loaded when their respective CHIP SELECT si~nals, CSl and CS3, are held low and the data present on the DATA IN line is ~locked in with the clock si~nal CLK where typically ~2 is loaded first and then U3 although, of course, the order could be reversed or provision could be made to simultaneously load U2 and U3 in parallel. .The LOAD/RUN line must also be held high while the shift registers are loaded from the DATA IN line. Once ~he registers U2 and U3 are loaded and the period length is shifted into them, the circuitxy is ready to gene-rate the R~ ON and RF DRIVE pulse trains. To generate these trains~ the LOAD/RUN line is held low and the external clock, - CLK~ is allowed to run. The data within the shif~ registers is then . shifted out serial-ly and simultaneously reloaded through input B.
The shift clock frequency is two times the funda-mental f requency of the RF ON and RF O~ pulse tr~ins .
~he modulation at a lower multiple frequency which was available in the circuitry of Fig. 2 is also present in the circuitry of Fig. 4, ~owever, in the circuitry of Fi~. 4 it is contained within the binary sequence which is loaded into shift reyisters U2 and U3. ~he binary sequence reguired to generate the R~ ON signal of FigO 3 is 10101010000000000000000000000000 and the RF OFF binary sequence is 0101010100000000D00~00000000 0000. The S~IFT clock freguency is one M~z, this, of course, being twice the fundamental frequency of 500 - . ~, . . .
`
. . -. ~ .
kH2. The progra~med length of the SHIFT register would be 32 bits, this corresponding to 2 latched wo~d in the hex fli~-flop Ul of 010000.
In comparing the first embodiment of Fig. 2 and the second emb~dim~nt of Fig. 4, it should be noted that in the first embodiment the fix2d length S~lFT
register is loaded with an ~F mas~ while in the second emDodiment, the SHI~T registers are loaded with the actual RF ON and RF O~F signals respectively. It should also be noted that the embodinlent of ~ig. 2 may also be employed in a configuration similar to that of Fig . 4 and vice versa . ~hat is, two f ixed lengths SHIYT re~isters may be used to respectivel~ generate the ~ ON and RP OFF signals as is done in Fig. 4. The 1~ RF ON signal would occur at ~) in Fig. 2 and the fYe-quenc~ select circuit including U2 for selecting the fundamental fre~uency bf the drive signal would be eliminated. The shift registers would each be clocked at a rate twice that of the desired fundamental fre-:- 2~ quency of the R~ ON an~ RF OFF pulses as is done in the ~ig. 4 embodiment. If the circuitry of Fig. 4 were utilized as in the Fig. 2 conf iguration, only one variable len~th S~IFT register would be used and would ::. be loaded with an R~ mask to ~re~u2ncy ~odulate a :75 frequ2nc~ selectable cl~ck sîg~al as is dQne in Fig. 2.
'-' ' ' . - ' ' .
' , ' , -~ ........................ .
O
Although two fixed length registers may be used in the ~i~. 4 configuration and a single variable lenyth SHI~T ~egister may be used in the FI~. 2 confîguration, the ~ig. 2 and Fig. 4 embodiments are .. , - ., -, : . , , ' , .
t~
the preferred embodiments for use of the ixed and variable length shift re~ister embo~iments respective-ly .
~1 may be a ~C14174, ~lEX D flip-flop; U~ and U3 may be MC14557's, 1 to 64 bit variable length shift ~ registers, and U4 may be an MC14071r ~uad 2-input OR
gate. Details on these circuits are described in ~otorola's CMOS databook or equivalent~ This cir-cuitry, as stated above, can also be either controlled b~ hardware o~ ~y a microprocessor.
~eference should now be made to Fi~ 5 wherein an erasable PR~M is utilized in lieu of the fixed and variable length shift registers of Figs~ 2 and 4. In particular, a. counter Ul is used to sequentially access the memory locations of an erasable P~o~
(EPROM~ U2 where the outputs of the EPROM are select-able by a multiplexer U3. The gate U4 allows resetting of the counter either by external means (not shown) or by a final count decode signal generated by a NAND
gate monitoring circuit U5 which includes a NAND gate and an inverter.
The EPROM is programmed with the binary formatted data corresponding to the various RF ON and RF OF~
drives. As will be discussed in more detail below with respect to ~ig~ 6 r the data ~or a qiven RF ON or RF
OFF driv~ is loaded se~uentially in memory and the various drives required are loaded in parallel. The ~inary formatted data of Fi~. 6 does not correspond to the actual binary formatted data typically employed for the various RF ON and R~ OFF drives~ However, this data has been chosen for ease of illustration of the invention. The EPROM extends vertically in Fig. 5;
however, once again for ease of illustration, the EPROM
is extended horizontally in Fi9. 6~ Thus, the EPRO~ is : . . . .. . . . . . . .
~-12~
8 bits wide and 64 bits long, it being divided into two banks where BA~K 1 extends from memory locations 0 through 31 while BANK 2 extends from memory locations 32 through 63. In actual practice the EPROM would typically be 8 bits wide while banks 1 and 2 would each be 1,024 locations long. An on/off signal applied to th~ BANK SELECT line selects either BANK 1 or BANK
~. If BANK 1 is selected, 0 is added to the binary count of counter Ul while if BANK 2 is selected 1,024 is added to the binary count. O$ course~ in the illustrative example of Fig. 6, 32 would be added to the binary count if BANK 2 were selected~ In BANK 1, ~ the on and of~ drive pulses for the CUT (Cu), BLEND 1 : IBl~, BLEND 2 (B2~, and ~LEND 3 (B3) signals are stored in BA~K 1. In particular, the ON wave~orm of the CUT binary formatted data is stored in the first bit of the successive memory locations of BANK 1. The CUT signal is a continu~us sequence of alternating ones and zeros. Thus, the period of this signal is two : 20 bits long, twelve periods of this signal are stored in . .
the first bits of the first twenty-four memory loca-tions of BANK 1 ~that is, memory locations 0 through 23). The first bits of khe remaining locations 24 : through 31 are not utilized for a reason which will be described below. The CUT RF OF~ binary formatted data is stored in the fifth bits of memory locations 0 through 23 of BANX 1. As can be seen this waveform is the inverse of the cut RF ON waveform. Again, memory locations 2d~ through 31 are not utilized.
The BLEND 1 RF ON binary data is stored in the second bits of memory locations 0 through 23. The illustrative period of this waveform is 8 bits long and the waveform itself constituting the se~uence ~ . . : . , .
~ 2~
1010000D. As can be seen in Fig. 6 this sequence is repeated three times to fill the second bits of memory locations 0 through 23. The BLEND 1 RF OFF binary data is stored in the sixth bits of memory locations 0 through 23 and, of course~ three periods of this waveform are also stored in the first twenty-~our memory locations. The RLEND 2 and BLEND 3 O~ and OFF
waveforms are respectively stored in the third, fourth~ seventh and eighth bits of the first twenty-four locations of BANK 1 where three per;ods of each of these waveforms is stored. Again, the memory loca-tions 24 through 31 are not utilized. Hence, none of the latter locations are utilized in BANK 1.
T~e COAG 1 and COAG 2 ON and OFF RF drive waveforms are respectively stored in the first, sec-ond, fifth and sixth bits of the first twenty-four memory locations of BA~K 2 ~-- that is, memory loca-tions 32 through 55. Again, the last 8 memory loca-: tions of the BANK are not utilize~ -- that is, loca-~ions 56 through 63. Moreo~er, none of the third, fourth, seventh or eighth bi.ts of any of the memory locations o~ the second BANR are utilized. Three periods of the COAG 1 ~or spray COAG) O~ and OFP
waveforms are respectively stored in the first and ; 25 fifth bi~s where one period of the COAG 1 ON waveform is 11000000 and one period of the OFF ~aveform is 00110000. Two periods of the COAG ON and OFF 2 wave-forms are respectivel~ stored in the second and sixth bits as can be seen in Fig. 6. It should be noted that 24 memory locations from each ba~k arê thus utilized to store all of the CUT and COAG wave~orms, as will be further discussed below.
In operation, assume it is desired to generate the BLENDED CUT (B3) ON and OFF RF drive pulses. The ~26~ ,?~
binary form~tted data Por th~ese pulses is stored in the ~ourth and eighth bits of BANK 1. Hence, the level of the sisnal on the BANK SELECT line will be at that level which will select BANK 1. Moreover, applied to the A and B inputs of the multiplexer will be a binary
, . ~ " '' , .., ', ` -:
Fig. 1 illustrates an electrosurgical generator ~5 10 connected to a patient circuit including an active electro~e 12 for appl~ing -electrosurgical current to a patient and a return electrode 14 for returning the ~ current to the generator. The generator includes a : pulse generator 16 having an RF drive output which 3U con~titutes a pulse train of varying configurations . . . . . .
., _3_ .
~2~
depending upon the mode of operation of the generator, The RF drive is applied to a switch 18, which when closed connects a supply voltage 19 across a tank circuit 20 comprising a capacitoc 22 and a primary coil 24, the ~ank being transformer coupled to a coil 26 in the patient circuit. Typically the resonant frequency of the tank equals the fundamental frequency of the pulse train applied to switch 18 when the mode of operatisn is one of the CUT modes while the funda-mental frequeney of th~ RF drive is typically one-half that of the resonant frequency of he tank when the mode of operation is one of the two COAG modes. of course, the number of modes may vary as well as.th~
frequency relationship between that of the resonant frequency of the tank and the fundamen~al frequency of the RF drive, A first illustrative embodiment of the pulse gene-rator 16 of ~ 1 is shown in Fig. 2 and includes a fixed length shift register Ulr a flip-flop U2, OR
gates U3 and ~3A, AND gate pairs U4 and U4A, inver~ers ~5 and U5A, a NAND gate flip-flip U~B and a totem pole drive including FET's 30 and 32. The RF DRIVE output ~how~ in Fig. l corresponds to the ou~put of the totem pole drive of Fig. 2. It is assumed in the followin~
description of the Fi9. 2 embodiment, the fundamental frequency of the RF DRIVE pulse train is either 500 kHz or 2S0 kHz. The different wave drives for the four-CUT waveforms and the two-COAG waveforms consist of the modulation of these two clock frequencies at a : 30 multiple of their respective fundamental where a basic clock signal of 500 k~z is applied to terminal 34.
In order to derive the clock freguencies of 500 k9z or 250 kHz a FREQUENCY SELECT circuit indicated at 33 ls em-loyed. Thi- circuit includes tlip-flop U2 : .. ,, , , . , ~ . ,, :
, .. ' ~ '' . ...
~2~7~3~3 which is configured as a toggle flip-flop. Its output Q is one-half the 500 kHz input signal applied thereto and thus the output of the flip-flop is 250 kHz. The 500 kHz input pulse traln is generated by circuitry not shown in a known manner. A ~REQUENCY SELECT line 36 is directly cuupled to one of the two parallel AND
gates U4 and through an inverter U5 to the other of the parallel AND gates U4. The signal on the FREQUENCY
SELECT line is a simple on/off signal which may be either m'icroprocessor generate~ or hardware generated in a known manner. The outputs of AND circuits U4 are connected to an OR circuit U3. Thus, if the FREQUENCY
SELECT line 36 is held high the output of ~3 will be 250 kHz since the output of the flip-flop will be : 15 gated through the upper AND gate U4 to the OR circuit.
If the line 36 is held low, the output of ~3 will be ~00 kHz since the 500 k~z input signal to the flip-~lop is also applied to the lower AND gate U4 : where it is ~ated to the OR circuit. The output of ~3 is directly applied to a first one of an A~D gate pair ~4A while thP inverse thereo$ is applied to the second - AND.gate of the pair via an inverter ~5A. The second input to the AND gates U4A is the serial output of the fixed length shift register Ul.
~ 25 The shift register is parallel loaded with an : 8-bit word, which may be considered an RF mask. It is loaded when the SHIFT/LOAD line PIN 1 of the register is held low. This line will be held low when the inputs to QR circuit U3A are held low. This occurs when an externally generated CHIP SELECT signal (nega-tive true), CS, and a WRITE PULSE tagain negative true~, WR, are applied to the OR gate via terminals 40 and 42. Hence, the OR gate basically performs an AND
function in that both the CHIP SELECT and ~RITE PULSE
signals must be present before the data on data bus line 38 can be parallel loacled into the shift regis-ter. The OR gate U3A may be used to effect communica-tion between a microprocessor and the shift register.
Alternatively, a hardware generated pulse could also be applied to the SHIFT/LOAD line to load the RF
mask. The fcregoing is true in all embodiments of the invention. That is, external control si~nals can either be hardware generated or generated under micro-processor control.
Once the shi~t register is loaded, the infor-mation therein may be shifted out serially at a rate corresponding to the clock rate present at its CLOCK
input line PIN 2. In the present description, the frequency of the clock is 250 kHz since the Q output of U2 is connected to PIN 2 of the register and since it has been assumed a 500 kHz signal is applied to the toggle flip-flop. The ~5~ kHz clock is suitable for present electrosurgical generators; however, the fre-quency of the shift clocked signal could also be selec-table according to generator requirements. As the RF
mask is shifted out of the shift register at PI~ g thereof, it is also serially reloaded back into the register at PIN 10 thereof. Accordingly, the shift re-2S gister is reloaded wit~ the preloaded ~F mask such that the mask is continually shifted out and reloaded - in a bit-by-bit progression. The output of the shift register is then ANDed with the fundamental clock frequency at the parallel gates of U4A~ The two clock signals, RF ON and RF OFF, are generated at the outputs of these AND circuits where they respectively set and reset the flip-flop comprising NAND gates U5B.
The Q output of the flip-flop is used as the gate drive for the totem pole drive arran~ement of FET's 30 `` ; 6 and 32. The common drain point of the F~T's is out-putted as an on-off pulse train for the RF stage. This corresponds to the RF DRIVE outpu~ from generator 16 of Fig. 1.
The reset ~ate of the NAND flip-flop U5B will, in practice, typically have a third input (not shown) which can be used to shut an RF pulse off before the R~ pulse is generated. This can be used as a means of curren~ feedback or over voltage shutdown. That is, if excessive current is sensed in the output circuit including tank 20 by sensing means (not shown), the sensing mean~ will apply a signal to the above mention-ed third input to effectively decrease the current in the output circuit in the manner described above. If other means are employed to compensate for over volt-age in the output circuit only the R~ ON DRIVE pulses need be generated where these may be directly applied ~o switch 18 of Fig. 1. In this instance, the NAND
gate flip-flop and the totem pole drive may be elimin-ated. The foregoing also applies to the remaining embodiments of the invention.
It should also be noted an edge coupler or dif-ferentiator tnoS shown) may typically be employed at the SET input to the flip-flop uSB so that the flip-flop is set by a short duration pulse. The above circuit elements have not been shown to simplify the explanation of the invention.
Typical integrated circuits which may be employed to implement the circuitry of Fig. 2 are as follows, it being understood these circuits are but illus-trative: shift register Ul, a 74LS165; flip-flop ~2, a 74LS74, dual D-type 1ip-flop, U3 and U3A, a 74LS32, quadruple 2~input positive-OR gates; U4 and U4A, a 74LS08, quadruple 2-input positive-AND gates; and U5, U5A and U5B~ a 74L~00, ~uadxuple 2-input pOSitiVe-NAND
gates. All of the above circuits are described in the TTL-Databookl Second Edition by Texas Instruments. The FET totem pole drive arranyement may comprise a PNP-NPN eombination of FET's. Information on this com-bination can be found in tbe databook of the Int~rna-10 . tional Rectifier Company.
Reference should now be made to Fig. 3 which depicts variou~ timing wave shapes to illustrate the operation of the circuitry of ~ig. ~. In particular, thesP wave shapes result in a twenty-five percent modulated fundamental frequency of ~00 kHz at a modula-tion fre~uency of 31.25 kHz. Such an RF drive pulse train is illustrated as the upper most wave shape in Fig. 3. Beneath this wave shape is illustrated the RF
mask loacled into the shift register Vl where the FREQUENCY SELECT line is low - tha~ is, zero. The encircled num~ers adjacent the remaining waveforms occur at those points in the Fig. 2 circuit where similar encircled numbers are indicated. Thus, after the mask is loaded in the register, the leading edge of each clock pulse applied to shi~t register ~1 causes the register to be shlfted one sta~e and the last stage to be outputted at PIN 9. The shape of the signal occurring at the output o the register is accordingly as shown at ~ since only the first two bits of the mask are l's. This output signal from the register ~requency modulates the 500 kHZ signals applied to AND gates U4A to provide the RF ON and RF
OFF signals shown at ~ and 0 . These in turn set and reset the flip-flop to drive the totem pole arrange-~ . . .
ment so that the RF DRIVE output from the totem pole follows the gate input at ~ and thus the desired RY
DRIVE pulse train is effected.
Reference should now be made to Fig. 4 which is directed to a second embodiment of the invention, it being characterized by variable length shift registers ~2 and U3. The length of the shift registers is controlled by the binary data set in HEX D flip-flop Ul. A single gate U~ is used to generate a clock or 1~ latching pulse for flip-flop Ul. The data present on the data bus at the time of the occurrence of the write pulse W.R will be latched into the flip-flop if the CHIP SELECT signal, CS2, is also present. As soon as the data is l~tched into the flip-flop, the length of ~he shift registers U2 and ~3 will be set.
The length of the shift registers, whieh ma~ be from 1 to 64 bits, is preferrably equal ~o a multiple of ~he period of the output RF ON and ~F OFF drive pulse : trains. These pulse trains are shown at the outputs of the shift registers and correspond to the RF ON and R~
: OFF pulse trains occurring at the outputs of AND gates U4A in Fig. 2. Thus, the NAND gate flip-flop U5B and totem pole drive of Fig. 2 are not shown in Fig. 4 and in .the subseguent embodiments of this invention al-. 25 though it is to be understood the RF O~ and RF O~F
.
: pulse trains of the embodiment of Fig. 4 and the other .
embodiments of this invention could typically be - applied to a NAND gate flip-flop and totem pole drive in the same manner as is illustrated in Fig. 2.
The length of the shift registers should be equal to a multiple of the period of the output RF ON and RF
OFF pulse drive trains. Thus, for a simple on-off-on-off type repetitive drive, the length would be a . , ., ~ , ., ' . .. .
.
.
~;s~
multiple of two~ For a drive with a configuration of on-off-off-off and then repeating a~ain, the length would be a multiple of four~ The actual length is thus determined by how many periods of the output wave shape are loaded into the shift registers.
The shift registers U2 and U3 are loaded when their respective CHIP SELECT si~nals, CSl and CS3, are held low and the data present on the DATA IN line is ~locked in with the clock si~nal CLK where typically ~2 is loaded first and then U3 although, of course, the order could be reversed or provision could be made to simultaneously load U2 and U3 in parallel. .The LOAD/RUN line must also be held high while the shift registers are loaded from the DATA IN line. Once ~he registers U2 and U3 are loaded and the period length is shifted into them, the circuitxy is ready to gene-rate the R~ ON and RF DRIVE pulse trains. To generate these trains~ the LOAD/RUN line is held low and the external clock, - CLK~ is allowed to run. The data within the shif~ registers is then . shifted out serial-ly and simultaneously reloaded through input B.
The shift clock frequency is two times the funda-mental f requency of the RF ON and RF O~ pulse tr~ins .
~he modulation at a lower multiple frequency which was available in the circuitry of Fig. 2 is also present in the circuitry of Fig. 4, ~owever, in the circuitry of Fi~. 4 it is contained within the binary sequence which is loaded into shift reyisters U2 and U3. ~he binary sequence reguired to generate the R~ ON signal of FigO 3 is 10101010000000000000000000000000 and the RF OFF binary sequence is 0101010100000000D00~00000000 0000. The S~IFT clock freguency is one M~z, this, of course, being twice the fundamental frequency of 500 - . ~, . . .
`
. . -. ~ .
kH2. The progra~med length of the SHIFT register would be 32 bits, this corresponding to 2 latched wo~d in the hex fli~-flop Ul of 010000.
In comparing the first embodiment of Fig. 2 and the second emb~dim~nt of Fig. 4, it should be noted that in the first embodiment the fix2d length S~lFT
register is loaded with an ~F mas~ while in the second emDodiment, the SHI~T registers are loaded with the actual RF ON and RF O~F signals respectively. It should also be noted that the embodinlent of ~ig. 2 may also be employed in a configuration similar to that of Fig . 4 and vice versa . ~hat is, two f ixed lengths SHIYT re~isters may be used to respectivel~ generate the ~ ON and RP OFF signals as is done in Fig. 4. The 1~ RF ON signal would occur at ~) in Fig. 2 and the fYe-quenc~ select circuit including U2 for selecting the fundamental fre~uency bf the drive signal would be eliminated. The shift registers would each be clocked at a rate twice that of the desired fundamental fre-:- 2~ quency of the R~ ON an~ RF OFF pulses as is done in the ~ig. 4 embodiment. If the circuitry of Fig. 4 were utilized as in the Fig. 2 conf iguration, only one variable len~th S~IFT register would be used and would ::. be loaded with an R~ mask to ~re~u2ncy ~odulate a :75 frequ2nc~ selectable cl~ck sîg~al as is dQne in Fig. 2.
'-' ' ' . - ' ' .
' , ' , -~ ........................ .
O
Although two fixed length registers may be used in the ~i~. 4 configuration and a single variable lenyth SHI~T ~egister may be used in the FI~. 2 confîguration, the ~ig. 2 and Fig. 4 embodiments are .. , - ., -, : . , , ' , .
t~
the preferred embodiments for use of the ixed and variable length shift re~ister embo~iments respective-ly .
~1 may be a ~C14174, ~lEX D flip-flop; U~ and U3 may be MC14557's, 1 to 64 bit variable length shift ~ registers, and U4 may be an MC14071r ~uad 2-input OR
gate. Details on these circuits are described in ~otorola's CMOS databook or equivalent~ This cir-cuitry, as stated above, can also be either controlled b~ hardware o~ ~y a microprocessor.
~eference should now be made to Fi~ 5 wherein an erasable PR~M is utilized in lieu of the fixed and variable length shift registers of Figs~ 2 and 4. In particular, a. counter Ul is used to sequentially access the memory locations of an erasable P~o~
(EPROM~ U2 where the outputs of the EPROM are select-able by a multiplexer U3. The gate U4 allows resetting of the counter either by external means (not shown) or by a final count decode signal generated by a NAND
gate monitoring circuit U5 which includes a NAND gate and an inverter.
The EPROM is programmed with the binary formatted data corresponding to the various RF ON and RF OF~
drives. As will be discussed in more detail below with respect to ~ig~ 6 r the data ~or a qiven RF ON or RF
OFF driv~ is loaded se~uentially in memory and the various drives required are loaded in parallel. The ~inary formatted data of Fi~. 6 does not correspond to the actual binary formatted data typically employed for the various RF ON and R~ OFF drives~ However, this data has been chosen for ease of illustration of the invention. The EPROM extends vertically in Fig. 5;
however, once again for ease of illustration, the EPROM
is extended horizontally in Fi9. 6~ Thus, the EPRO~ is : . . . .. . . . . . . .
~-12~
8 bits wide and 64 bits long, it being divided into two banks where BA~K 1 extends from memory locations 0 through 31 while BANK 2 extends from memory locations 32 through 63. In actual practice the EPROM would typically be 8 bits wide while banks 1 and 2 would each be 1,024 locations long. An on/off signal applied to th~ BANK SELECT line selects either BANK 1 or BANK
~. If BANK 1 is selected, 0 is added to the binary count of counter Ul while if BANK 2 is selected 1,024 is added to the binary count. O$ course~ in the illustrative example of Fig. 6, 32 would be added to the binary count if BANK 2 were selected~ In BANK 1, ~ the on and of~ drive pulses for the CUT (Cu), BLEND 1 : IBl~, BLEND 2 (B2~, and ~LEND 3 (B3) signals are stored in BA~K 1. In particular, the ON wave~orm of the CUT binary formatted data is stored in the first bit of the successive memory locations of BANK 1. The CUT signal is a continu~us sequence of alternating ones and zeros. Thus, the period of this signal is two : 20 bits long, twelve periods of this signal are stored in . .
the first bits of the first twenty-four memory loca-tions of BANK 1 ~that is, memory locations 0 through 23). The first bits of khe remaining locations 24 : through 31 are not utilized for a reason which will be described below. The CUT RF OF~ binary formatted data is stored in the fifth bits of memory locations 0 through 23 of BANX 1. As can be seen this waveform is the inverse of the cut RF ON waveform. Again, memory locations 2d~ through 31 are not utilized.
The BLEND 1 RF ON binary data is stored in the second bits of memory locations 0 through 23. The illustrative period of this waveform is 8 bits long and the waveform itself constituting the se~uence ~ . . : . , .
~ 2~
1010000D. As can be seen in Fig. 6 this sequence is repeated three times to fill the second bits of memory locations 0 through 23. The BLEND 1 RF OFF binary data is stored in the sixth bits of memory locations 0 through 23 and, of course~ three periods of this waveform are also stored in the first twenty-~our memory locations. The RLEND 2 and BLEND 3 O~ and OFF
waveforms are respectively stored in the third, fourth~ seventh and eighth bits of the first twenty-four locations of BANK 1 where three per;ods of each of these waveforms is stored. Again, the memory loca-tions 24 through 31 are not utilized. Hence, none of the latter locations are utilized in BANK 1.
T~e COAG 1 and COAG 2 ON and OFF RF drive waveforms are respectively stored in the first, sec-ond, fifth and sixth bits of the first twenty-four memory locations of BA~K 2 ~-- that is, memory loca-tions 32 through 55. Again, the last 8 memory loca-: tions of the BANK are not utilize~ -- that is, loca-~ions 56 through 63. Moreo~er, none of the third, fourth, seventh or eighth bi.ts of any of the memory locations o~ the second BANR are utilized. Three periods of the COAG 1 ~or spray COAG) O~ and OFP
waveforms are respectively stored in the first and ; 25 fifth bi~s where one period of the COAG 1 ON waveform is 11000000 and one period of the OFF ~aveform is 00110000. Two periods of the COAG ON and OFF 2 wave-forms are respectivel~ stored in the second and sixth bits as can be seen in Fig. 6. It should be noted that 24 memory locations from each ba~k arê thus utilized to store all of the CUT and COAG wave~orms, as will be further discussed below.
In operation, assume it is desired to generate the BLENDED CUT (B3) ON and OFF RF drive pulses. The ~26~ ,?~
binary form~tted data Por th~ese pulses is stored in the ~ourth and eighth bits of BANK 1. Hence, the level of the sisnal on the BANK SELECT line will be at that level which will select BANK 1. Moreover, applied to the A and B inputs of the multiplexer will be a binary
3 -- that is, the DRIVE SELECT 0 and DRIVE SELECT 1 lines will both have high levels or ones applied thereto, which will cause the multiplexer to select the outputs from the fo~ ;h and eightb ~its of each - 10 memory location as that location is accessed by counter Ul.
Assuming the counter has been reset, it will begin counting as soon as the CLOCK applied to PIN 10 is allowed to run the count, of course, bèginning from zero. ~hen the number zero is applied to the PROM, the zero (or first) memory location will be accessed where-by the first throu~h eighth bits of the first loc~tion will be respectively applied to the output PI~S 0 through 7 of the PROM. In particular, the binary 2~ sequence 11110000 will be applied to these QUtpUts ~rom the first BANK. Since the multiplexer has been set to select the fourth and eighth bits of ea~h accessed memory location, the bit 1 will be applied to the ~F ON output line of the multiplexer while the bit 3 will be applied to the RF O~F line. When the counter steps to 1, the second memory location is accessed to apply the sequence 00001111 to the multiplexer where again the fourth and eighth bits are selected to apply the bits D and 1 as RF ON and OFF outputs respective-ly. In this manner, the successive binary outputs of counter Ul are decoded in U2 to effect sequential accessing of the successive memory locations of the P~O~ to generate the B3 RF ON and OFF pulse trains.
, ~ , . - , .
-15- .
~lZ~
~7hen the counter reaches the binary value of 23 (that is, the last memory location where a B3 data bit is stored~, the conditions or the NAND gate U5 will be satisfied to generate a reset pulse through ~4 to reset the counter to its zero value. The counter will again step through 24 counts to generate thre~ more periods of the B3 waveform. Thus, the B3 waveform will be generated as long as the CLOCK is applied to the counter.
From the foregoing it is clear the counter resets after 24 memory locations have been accessed. More-over, as described above, all of the CUT and COAG
waveforms occupy the first twenty-four memory loca~
tions of either BANX 1 or BANK 2. Thus, regardless of whether a CUT or COAG signal has been selected9 the same NA~D gate U5 can be employed to effect resetting of the counter and, of course, recycling of the vari-ous RF ON and OPF drives. 1`his has been e~fected by noting that the period of the CVT waveform is two bits long while the period length of the blended cuts and the COAG 1 waveforms is 8 bits and the period length of the COAG 2 waveform is 12 bits. Thus, the lowest common multiple of the numb~ers 2, 8, and 12 is 24~
~ence, by storing the number of periods of each wave-form necessary to occupy 24 memory locations, the simple NAND gate U5 can be employed to reset the counter at the common count of 24 to thus provide a simple circuit for generating all of the waveforms.
~s noted above, each of the BANKS is 32 memory locations long. Since the lowest common multiple of the period lengths of the different waveforms is 24, it is not necessary to use the remaining eight loca-tions of each ~A~K.
~ -16-. .
From the foregoing it can be seen that the BANK
SELECT si~nal (either high or low) determines whether the output will be a CUT or COAG signal. The four CUT
signals are selected by the combination of signals applied to the A and B inputs of the multiplexer U3 where, for example, low signals applied to each of these inputs would select the CU~ ON and OFF RF
signals, a high signal applied to terminal A and a low signal applied to terminal B would select the blended CUT (Bl~ signals, a low signal applied to terminal A
and a high signal to terminal B would select the 32 signals and,- as described in detail above, high sig-nals applied to the A and B terminals select the B3 signals. The foregoing, of course, assumes the first BANK has been selected~ If the second BAMR is select-ed, 32 is added within U2 to the output of counter ~1 to select the second bank and the COAG 1 signals are selected by applying low signals to the A and B
terminals of the multiplexer while the COAG 2 signals are selected by applying a hi~h signal to terminal A
and a low signal to terminal B.
As stated above, the binary formatted data employ ed in Fig. 6 is illustrative. In actu~l practice, the length of the period of a CUT signal would be tw~ bits as shown in Fig. 6. However~ the length of the period of the blended CUT signals is each 48 bits as is the COAG 1 waveform while the period of the COAG 2 wave-form is 68 bits. The lowest common multiple of these . numbers is 816..... Thus NAND gate U5 is set to be : 30 responsive to that num~er as is illustrated in Fi~. 5 to effect c~clic resetting of the counter.
In summar~, external circuitry selects which BAN~
is to be accessed. The BANK SELECT allows up to ei~ht : , . ... . :
3~
pairs o~ RF ON and RY OFF drives to be stored in memory at one time where in the pres~nt embodiment only six pairs are stored. Once a BANIC has been selected and counter ~1 has been reset, the multiplex-er DRIVE SELECT lines are set to determine which ~ns of the four drive pairs is to be selected. Then ,he C~OCK is allo-~2d to run and the counter begins counting.
The memory locations of the PRO~ are then seguQn-tiall~,r accessed and the eight-bit wide words at the : memory locations sequentially appear at the inputs to the multiplexer. Only those two 5 ignals s~lected by the DRIVE S~LECT lines are transmitted through the multiplexer and appear at the ~F ON and RF OFF outpu~
lS terminals. The pulse train generated is therefor the sequential data bits stored in a given data position within the EPROM.
The embodiment of Fig. 5 results in a lea~t par~s .count or a circuit which has a si~nal with frequencies of .
~0 '750 kBz (CUT), 81.25 `~Z tthe blended CUT and ~OAG 1 si~nals), and 22~05 k8z tthe COAG 2 si~nal). The fundamental frequencies employed in this embod~ment would be 750 k~æ and 375 Ic~z. Thus the input ~lock rate to the counter would respectively be 1.5 mH~ and ~5 75~ kHz ~or these ~wo fundamental fre~uencies. A~ the 1.5 mHz clock rate the number of ~iemory loca~ions reguired for the three above periods are 2, 48, and - 68. It is possible to have ~he end point of th~
coun'er be selectable for these three lengths however, the chip count wDuld be high. Thus, in accordance with the embodiment o~ Fig. 5, one end count is provide~ -for all o~ the periods and the desired signals are repeated a number of times for those signals which are ~ . . .. . .. .. . . . . . ....
~Z~7~ ~
shorter than the end count. Although, as stated above, an end count of 48 would suffice for the CUT and COAG
1 signals, it would not for the COAG 2 signal, which requi~es an end count of 68. Thus, the least common multiple of 816 permits a common end count suitable for all drives which can be detected by a single chip U5. Since 816 is less than the 1,024 lengths of BANKS
1 and 2, all requirements are satisfied.
Thus all that is required is to load the PROM
sequentially with the required binary information for the six RE ON and six RF OFF driYe trains. For the C~T
train, the signal is repeated 4D8 times, the BLE~DED
CUTS AND COAG 17 times, and the COAG 2 train 12 times.
Although some redundancy occurs, the final decode cir-cuit U5 for 816 becomes a single four input NAND gate and an inverter~ This, as stated above, resets the counter to start the counting from zero again when the final count is reached in a simple and straight~orward manner.
Typical components which may be employed in the embodiment of Fig. 5 are as follows where it is again to be understood these components are illustative and the invention is no~ limited thereto: Ul may be a MC}4040, 12-bit binary count~er, U2 may be a 2716, 2KX8 W erasable PROM; ~3 may be a dual 4-channel analog multiplexer; U4 may be a Mc14071, quad 2-input OR
~-- GATE; and U5 a MC14012 dual 4-input NAND gate.
There are several variations of the third embodi-ment which are possible, although the embodiment of Fig. 5 is preferred. ~he PROM can be replaced by a RAM
and a microprocessor can load the device specifically for the DRIVE train required so that the output multi-plexer is not required. The same two output data bits ..
'' . ' , . ,., , ,,, ~, . . . .
` , ~19-~r~ alw~y~ used ~or the ~F 0~ a~d R~ 0~ ~ignals, for example, the fir~t and fiftb output data terminal~ for ~he CUT signals. The decode circuitry U5 can al~o be i~plementad by latching the Pin~l count into a MC
14174~ H~X D type flip-flop, or gguivalent ~nd comp~r-ing the ma~nitude of addre~s coun er Ul to the final coun~ ~et in the flip-flop~ ~hen the two counts are equal the coun~er would be r~etO ~ circuit whi~h compare~ the counts i~ a 74LS85, ~ four bit m~nitu~e co~par~tor, Again, as in the last example~ the RF ON and ~F
O~F DRIVE output8 are st~e~d to the ~AND gat~ flip-flop to set al d re~et it to drive the gates of the ~ET
totem pole to genera~e the actual RF DRIVE signal.
- 1~ It should also be noted that although the outputs fro~ the various storage devices ha~e been taken ~e-quentia~lly, they could al80 be t~ken ~n p~ral~el an~
~pplied to a parallel-tv-serial conv~r~t~r or ~he lik~
to develop the desired pulse train~ These and other ~imilar modifi~ations will be apparen~ to those ~kill-. ed in this ~rt.
~'~ ' , ' ' '. . ' .
. . . ...
~ ~ ' ' . - " ' " ' ' ' . . ' " " ' ' , - ' .
' ' ' ' " ' '' ' ' ' " ' ' ' . ' '' ' .' " ' '. ':, ' ~ .' ' ' . ' . . ' ~:
.,, ~ . . - . . .
.. . . . . . . . . . - . . . .
,' ' '. . ' - ' ' - . ,. ` . -, . ~ . ' '' . ' . . ' , ' .
. . . ~ . .. . . . ..
:
Assuming the counter has been reset, it will begin counting as soon as the CLOCK applied to PIN 10 is allowed to run the count, of course, bèginning from zero. ~hen the number zero is applied to the PROM, the zero (or first) memory location will be accessed where-by the first throu~h eighth bits of the first loc~tion will be respectively applied to the output PI~S 0 through 7 of the PROM. In particular, the binary 2~ sequence 11110000 will be applied to these QUtpUts ~rom the first BANK. Since the multiplexer has been set to select the fourth and eighth bits of ea~h accessed memory location, the bit 1 will be applied to the ~F ON output line of the multiplexer while the bit 3 will be applied to the RF O~F line. When the counter steps to 1, the second memory location is accessed to apply the sequence 00001111 to the multiplexer where again the fourth and eighth bits are selected to apply the bits D and 1 as RF ON and OFF outputs respective-ly. In this manner, the successive binary outputs of counter Ul are decoded in U2 to effect sequential accessing of the successive memory locations of the P~O~ to generate the B3 RF ON and OFF pulse trains.
, ~ , . - , .
-15- .
~lZ~
~7hen the counter reaches the binary value of 23 (that is, the last memory location where a B3 data bit is stored~, the conditions or the NAND gate U5 will be satisfied to generate a reset pulse through ~4 to reset the counter to its zero value. The counter will again step through 24 counts to generate thre~ more periods of the B3 waveform. Thus, the B3 waveform will be generated as long as the CLOCK is applied to the counter.
From the foregoing it is clear the counter resets after 24 memory locations have been accessed. More-over, as described above, all of the CUT and COAG
waveforms occupy the first twenty-four memory loca~
tions of either BANX 1 or BANK 2. Thus, regardless of whether a CUT or COAG signal has been selected9 the same NA~D gate U5 can be employed to effect resetting of the counter and, of course, recycling of the vari-ous RF ON and OPF drives. 1`his has been e~fected by noting that the period of the CVT waveform is two bits long while the period length of the blended cuts and the COAG 1 waveforms is 8 bits and the period length of the COAG 2 waveform is 12 bits. Thus, the lowest common multiple of the numb~ers 2, 8, and 12 is 24~
~ence, by storing the number of periods of each wave-form necessary to occupy 24 memory locations, the simple NAND gate U5 can be employed to reset the counter at the common count of 24 to thus provide a simple circuit for generating all of the waveforms.
~s noted above, each of the BANKS is 32 memory locations long. Since the lowest common multiple of the period lengths of the different waveforms is 24, it is not necessary to use the remaining eight loca-tions of each ~A~K.
~ -16-. .
From the foregoing it can be seen that the BANK
SELECT si~nal (either high or low) determines whether the output will be a CUT or COAG signal. The four CUT
signals are selected by the combination of signals applied to the A and B inputs of the multiplexer U3 where, for example, low signals applied to each of these inputs would select the CU~ ON and OFF RF
signals, a high signal applied to terminal A and a low signal applied to terminal B would select the blended CUT (Bl~ signals, a low signal applied to terminal A
and a high signal to terminal B would select the 32 signals and,- as described in detail above, high sig-nals applied to the A and B terminals select the B3 signals. The foregoing, of course, assumes the first BANK has been selected~ If the second BAMR is select-ed, 32 is added within U2 to the output of counter ~1 to select the second bank and the COAG 1 signals are selected by applying low signals to the A and B
terminals of the multiplexer while the COAG 2 signals are selected by applying a hi~h signal to terminal A
and a low signal to terminal B.
As stated above, the binary formatted data employ ed in Fig. 6 is illustrative. In actu~l practice, the length of the period of a CUT signal would be tw~ bits as shown in Fig. 6. However~ the length of the period of the blended CUT signals is each 48 bits as is the COAG 1 waveform while the period of the COAG 2 wave-form is 68 bits. The lowest common multiple of these . numbers is 816..... Thus NAND gate U5 is set to be : 30 responsive to that num~er as is illustrated in Fi~. 5 to effect c~clic resetting of the counter.
In summar~, external circuitry selects which BAN~
is to be accessed. The BANK SELECT allows up to ei~ht : , . ... . :
3~
pairs o~ RF ON and RY OFF drives to be stored in memory at one time where in the pres~nt embodiment only six pairs are stored. Once a BANIC has been selected and counter ~1 has been reset, the multiplex-er DRIVE SELECT lines are set to determine which ~ns of the four drive pairs is to be selected. Then ,he C~OCK is allo-~2d to run and the counter begins counting.
The memory locations of the PRO~ are then seguQn-tiall~,r accessed and the eight-bit wide words at the : memory locations sequentially appear at the inputs to the multiplexer. Only those two 5 ignals s~lected by the DRIVE S~LECT lines are transmitted through the multiplexer and appear at the ~F ON and RF OFF outpu~
lS terminals. The pulse train generated is therefor the sequential data bits stored in a given data position within the EPROM.
The embodiment of Fig. 5 results in a lea~t par~s .count or a circuit which has a si~nal with frequencies of .
~0 '750 kBz (CUT), 81.25 `~Z tthe blended CUT and ~OAG 1 si~nals), and 22~05 k8z tthe COAG 2 si~nal). The fundamental frequencies employed in this embod~ment would be 750 k~æ and 375 Ic~z. Thus the input ~lock rate to the counter would respectively be 1.5 mH~ and ~5 75~ kHz ~or these ~wo fundamental fre~uencies. A~ the 1.5 mHz clock rate the number of ~iemory loca~ions reguired for the three above periods are 2, 48, and - 68. It is possible to have ~he end point of th~
coun'er be selectable for these three lengths however, the chip count wDuld be high. Thus, in accordance with the embodiment o~ Fig. 5, one end count is provide~ -for all o~ the periods and the desired signals are repeated a number of times for those signals which are ~ . . .. . .. .. . . . . . ....
~Z~7~ ~
shorter than the end count. Although, as stated above, an end count of 48 would suffice for the CUT and COAG
1 signals, it would not for the COAG 2 signal, which requi~es an end count of 68. Thus, the least common multiple of 816 permits a common end count suitable for all drives which can be detected by a single chip U5. Since 816 is less than the 1,024 lengths of BANKS
1 and 2, all requirements are satisfied.
Thus all that is required is to load the PROM
sequentially with the required binary information for the six RE ON and six RF OFF driYe trains. For the C~T
train, the signal is repeated 4D8 times, the BLE~DED
CUTS AND COAG 17 times, and the COAG 2 train 12 times.
Although some redundancy occurs, the final decode cir-cuit U5 for 816 becomes a single four input NAND gate and an inverter~ This, as stated above, resets the counter to start the counting from zero again when the final count is reached in a simple and straight~orward manner.
Typical components which may be employed in the embodiment of Fig. 5 are as follows where it is again to be understood these components are illustative and the invention is no~ limited thereto: Ul may be a MC}4040, 12-bit binary count~er, U2 may be a 2716, 2KX8 W erasable PROM; ~3 may be a dual 4-channel analog multiplexer; U4 may be a Mc14071, quad 2-input OR
~-- GATE; and U5 a MC14012 dual 4-input NAND gate.
There are several variations of the third embodi-ment which are possible, although the embodiment of Fig. 5 is preferred. ~he PROM can be replaced by a RAM
and a microprocessor can load the device specifically for the DRIVE train required so that the output multi-plexer is not required. The same two output data bits ..
'' . ' , . ,., , ,,, ~, . . . .
` , ~19-~r~ alw~y~ used ~or the ~F 0~ a~d R~ 0~ ~ignals, for example, the fir~t and fiftb output data terminal~ for ~he CUT signals. The decode circuitry U5 can al~o be i~plementad by latching the Pin~l count into a MC
14174~ H~X D type flip-flop, or gguivalent ~nd comp~r-ing the ma~nitude of addre~s coun er Ul to the final coun~ ~et in the flip-flop~ ~hen the two counts are equal the coun~er would be r~etO ~ circuit whi~h compare~ the counts i~ a 74LS85, ~ four bit m~nitu~e co~par~tor, Again, as in the last example~ the RF ON and ~F
O~F DRIVE output8 are st~e~d to the ~AND gat~ flip-flop to set al d re~et it to drive the gates of the ~ET
totem pole to genera~e the actual RF DRIVE signal.
- 1~ It should also be noted that although the outputs fro~ the various storage devices ha~e been taken ~e-quentia~lly, they could al80 be t~ken ~n p~ral~el an~
~pplied to a parallel-tv-serial conv~r~t~r or ~he lik~
to develop the desired pulse train~ These and other ~imilar modifi~ations will be apparen~ to those ~kill-. ed in this ~rt.
~'~ ' , ' ' '. . ' .
. . . ...
~ ~ ' ' . - " ' " ' ' ' . . ' " " ' ' , - ' .
' ' ' ' " ' '' ' ' ' " ' ' ' . ' '' ' .' " ' '. ':, ' ~ .' ' ' . ' . . ' ~:
.,, ~ . . - . . .
.. . . . . . . . . . - . . . .
,' ' '. . ' - ' ' - . ,. ` . -, . ~ . ' '' . ' . . ' , ' .
. . . ~ . .. . . . ..
:
Claims (10)
PROPERTY OR PRIVILEGE IS CLAIMED ARE DEFINED AS FOLLOWS:
1. An electrosurgical generator comprising a patient circuit including an active electrode and a return electrode; and means for generating a pulse train in said generator, characterized in that said pulse train generating means includes at least one MXN storage device having M memory locations where M > 1 and where each location contains N storage positions where N ? 1, said storage device storing at least one, K-bit binary signal, where 1 < K ? M bits of which are respectively stored in the Jth storage positions of K of the M memory locations where J ? N;
means for sequentially outputting said K-bit binary signal from said storage device; and electrosurgical signal generating means responsive to the K-bit binary signal for generating an electrosurgical signal and applying this signal to the patient circuit.
means for sequentially outputting said K-bit binary signal from said storage device; and electrosurgical signal generating means responsive to the K-bit binary signal for generating an electrosurgical signal and applying this signal to the patient circuit.
2. A generator according to claim 1 characterized in that the storage device is a shift register (N = 1).
3. A generator according to claim 2 characterized in that the register is a fixed length register or a variable length register.
4. A generator according to claim 1, characterized in that the storage device is a read-only memory.
5. A generator according to any one of claims 1 to 3 characterized by including at least two of the storage devices where each stores a said K-bit binary signal, the electrosurgical generating means being responsive to both of said K-bit binary signals to generate the electrosurgical signal.
6. A generator according to any one of claims 1 to 3, characterized in that the storage device stores a plurality of binary signals, at least one of which is said K bits in length and the other of which is H bits in length where 1 < H ? M.
7. A generator according to claim 1 characterized in that N > 1 and the storage device stores Q of the K-bit binary signals where 1 < Q ? N, the K-bit binary signals being respectively stored in the Jth storage positions of the K memory locations where J - 1, 2, ..., Q, each of said K-bit binary signals respectively has a unique configuration of ON and OFF states corresponding to a particular mode of operation of the generator, and the generator includes means for selecting, as an output from said storage device, one of the K-bit binary signals, the electrosurgical signal generating means being responsive to the selected K-bit binary signals to generate the electrosurgical signal.
8. The generator according to claim 7, characterized in that at least one of the K-bit binary signals contains a plurality of periods of a basic sequence of the ON and OFF states representative of the generator mode of operation corresponding to the one K-bit binary signals and where the means for sequentially ouputting the K-bit binary signal includes a counter for sequentially accessing the memory locations and decoding means response to the counter output for resetting the counter to its initial count each time it counts to K.
9. A generator according to claim 7, characterized in that the storage device is divided into P banks where the number of memory locations in each bank is M/P and where K ? M/P, at least one of said K-bit binary signals being stored in the Jth storage positions of K of the M/P memory locations of one of the banks where J ? N and at least another one of the K-bit binary signals being stored in the Rth storage positions of K of the M/P memory locations of another one of the banks where R ? N.
10. A generator according to anyone of claims 1 to 3 characterized In that the storage device stores Q
pairs of the K-bit binary signals where 1 ? Q ? N/2, the first one of each pair of K-bit binary signals being respectively stored in the Sth storage positions of the K memory locations where S = 1, 2, ... Q/2 and the second one of each pair being respectively stored in the Tth storage positions of the X memory locations where T = Q/2 + 1, Q/2 + 2, ... , Q, and each of the pairs corresponds to a particular mode of operation of the generator and the generator includes means for selecting, as an output from said storage device, one of the pairs of K-bit binary signals, the electrosurgical signals generating means being response to the selected pair of K-bit signals to generate the electrosurgical signal.
pairs of the K-bit binary signals where 1 ? Q ? N/2, the first one of each pair of K-bit binary signals being respectively stored in the Sth storage positions of the K memory locations where S = 1, 2, ... Q/2 and the second one of each pair being respectively stored in the Tth storage positions of the X memory locations where T = Q/2 + 1, Q/2 + 2, ... , Q, and each of the pairs corresponds to a particular mode of operation of the generator and the generator includes means for selecting, as an output from said storage device, one of the pairs of K-bit binary signals, the electrosurgical signals generating means being response to the selected pair of K-bit signals to generate the electrosurgical signal.
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| US06/704,188 US4658820A (en) | 1985-02-22 | 1985-02-22 | Electrosurgical generator with improved circuitry for generating RF drive pulse trains |
| US704,188 | 1985-02-22 |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CA1267438A true CA1267438A (en) | 1990-04-03 |
Family
ID=24828458
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CA000502333A Expired - Lifetime CA1267438A (en) | 1985-02-22 | 1986-02-20 | Electrosurgical generator with improved circuitry for generating rf drive pulse trains |
Country Status (8)
| Country | Link |
|---|---|
| US (1) | US4658820A (en) |
| EP (1) | EP0194078A3 (en) |
| JP (1) | JPH0728872B2 (en) |
| AU (1) | AU574565B2 (en) |
| CA (1) | CA1267438A (en) |
| DK (1) | DK81186A (en) |
| FI (1) | FI860772A (en) |
| NO (1) | NO860815L (en) |
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- 1986-02-21 AU AU53865/86A patent/AU574565B2/en not_active Expired
- 1986-02-21 DK DK081186A patent/DK81186A/en not_active Application Discontinuation
- 1986-02-21 FI FI860772A patent/FI860772A/en not_active Application Discontinuation
- 1986-02-22 JP JP61038126A patent/JPH0728872B2/en not_active Expired - Lifetime
- 1986-03-04 NO NO860815A patent/NO860815L/en unknown
Also Published As
| Publication number | Publication date |
|---|---|
| EP0194078A3 (en) | 1988-03-09 |
| JPS61222441A (en) | 1986-10-02 |
| FI860772A0 (en) | 1986-02-21 |
| DK81186A (en) | 1986-08-23 |
| AU5386586A (en) | 1986-08-28 |
| DK81186D0 (en) | 1986-02-21 |
| FI860772A (en) | 1986-08-23 |
| EP0194078A2 (en) | 1986-09-10 |
| NO860815L (en) | 1987-09-07 |
| AU574565B2 (en) | 1988-07-07 |
| US4658820A (en) | 1987-04-21 |
| JPH0728872B2 (en) | 1995-04-05 |
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Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| MKEX | Expiry |